- •Analysis and Application of Analog Electronic Circuits to Biomedical Instrumentation
- •Dedication
- •Preface
- •Reader Background
- •Rationale
- •Description of the Chapters
- •Features
- •The Author
- •Table of Contents
- •1.1 Introduction
- •1.2 Sources of Endogenous Bioelectric Signals
- •1.3 Nerve Action Potentials
- •1.4 Muscle Action Potentials
- •1.4.1 Introduction
- •1.4.2 The Origin of EMGs
- •1.5 The Electrocardiogram
- •1.5.1 Introduction
- •1.6 Other Biopotentials
- •1.6.1 Introduction
- •1.6.2 EEGs
- •1.6.3 Other Body Surface Potentials
- •1.7 Discussion
- •1.8 Electrical Properties of Bioelectrodes
- •1.9 Exogenous Bioelectric Signals
- •1.10 Chapter Summary
- •2.1 Introduction
- •2.2.1 Introduction
- •2.2.4 Schottky Diodes
- •2.3.1 Introduction
- •2.4.1 Introduction
- •2.5.1 Introduction
- •2.5.5 Broadbanding Strategies
- •2.6 Photons, Photodiodes, Photoconductors, LEDs, and Laser Diodes
- •2.6.1 Introduction
- •2.6.2 PIN Photodiodes
- •2.6.3 Avalanche Photodiodes
- •2.6.4 Signal Conditioning Circuits for Photodiodes
- •2.6.5 Photoconductors
- •2.6.6 LEDs
- •2.6.7 Laser Diodes
- •2.7 Chapter Summary
- •Home Problems
- •3.1 Introduction
- •3.2 DA Circuit Architecture
- •3.4 CM and DM Gain of Simple DA Stages at High Frequencies
- •3.4.1 Introduction
- •3.5 Input Resistance of Simple Transistor DAs
- •3.7 How Op Amps Can Be Used To Make DAs for Medical Applications
- •3.7.1 Introduction
- •3.8 Chapter Summary
- •Home Problems
- •4.1 Introduction
- •4.3 Some Effects of Negative Voltage Feedback
- •4.3.1 Reduction of Output Resistance
- •4.3.2 Reduction of Total Harmonic Distortion
- •4.3.4 Decrease in Gain Sensitivity
- •4.4 Effects of Negative Current Feedback
- •4.5 Positive Voltage Feedback
- •4.5.1 Introduction
- •4.6 Chapter Summary
- •Home Problems
- •5.1 Introduction
- •5.2.1 Introduction
- •5.2.2 Bode Plots
- •5.5.1 Introduction
- •5.5.3 The Wien Bridge Oscillator
- •5.6 Chapter Summary
- •Home Problems
- •6.1 Ideal Op Amps
- •6.1.1 Introduction
- •6.1.2 Properties of Ideal OP Amps
- •6.1.3 Some Examples of OP Amp Circuits Analyzed Using IOAs
- •6.2 Practical Op Amps
- •6.2.1 Introduction
- •6.2.2 Functional Categories of Real Op Amps
- •6.3.1 The GBWP of an Inverting Summer
- •6.4.3 Limitations of CFOAs
- •6.5 Voltage Comparators
- •6.5.1 Introduction
- •6.5.2. Applications of Voltage Comparators
- •6.5.3 Discussion
- •6.6 Some Applications of Op Amps in Biomedicine
- •6.6.1 Introduction
- •6.6.2 Analog Integrators and Differentiators
- •6.7 Chapter Summary
- •Home Problems
- •7.1 Introduction
- •7.2 Types of Analog Active Filters
- •7.2.1 Introduction
- •7.2.3 Biquad Active Filters
- •7.2.4 Generalized Impedance Converter AFs
- •7.3 Electronically Tunable AFs
- •7.3.1 Introduction
- •7.3.3 Use of Digitally Controlled Potentiometers To Tune a Sallen and Key LPF
- •7.5 Chapter Summary
- •7.5.1 Active Filters
- •7.5.2 Choice of AF Components
- •Home Problems
- •8.1 Introduction
- •8.2 Instrumentation Amps
- •8.3 Medical Isolation Amps
- •8.3.1 Introduction
- •8.3.3 A Prototype Magnetic IsoA
- •8.4.1 Introduction
- •8.6 Chapter Summary
- •9.1 Introduction
- •9.2 Descriptors of Random Noise in Biomedical Measurement Systems
- •9.2.1 Introduction
- •9.2.2 The Probability Density Function
- •9.2.3 The Power Density Spectrum
- •9.2.4 Sources of Random Noise in Signal Conditioning Systems
- •9.2.4.1 Noise from Resistors
- •9.2.4.3 Noise in JFETs
- •9.2.4.4 Noise in BJTs
- •9.3 Propagation of Noise through LTI Filters
- •9.4.2 Spot Noise Factor and Figure
- •9.5.1 Introduction
- •9.6.1 Introduction
- •9.7 Effect of Feedback on Noise
- •9.7.1 Introduction
- •9.8.1 Introduction
- •9.8.2 Calculation of the Minimum Resolvable AC Input Voltage to a Noisy Op Amp
- •9.8.5.1 Introduction
- •9.8.5.2 Bridge Sensitivity Calculations
- •9.8.7.1 Introduction
- •9.8.7.2 Analysis of SNR Improvement by Averaging
- •9.8.7.3 Discussion
- •9.10.1 Introduction
- •9.11 Chapter Summary
- •Home Problems
- •10.1 Introduction
- •10.2 Aliasing and the Sampling Theorem
- •10.2.1 Introduction
- •10.2.2 The Sampling Theorem
- •10.3 Digital-to-Analog Converters (DACs)
- •10.3.1 Introduction
- •10.3.2 DAC Designs
- •10.3.3 Static and Dynamic Characteristics of DACs
- •10.4 Hold Circuits
- •10.5 Analog-to-Digital Converters (ADCs)
- •10.5.1 Introduction
- •10.5.2 The Tracking (Servo) ADC
- •10.5.3 The Successive Approximation ADC
- •10.5.4 Integrating Converters
- •10.5.5 Flash Converters
- •10.6 Quantization Noise
- •10.7 Chapter Summary
- •Home Problems
- •11.1 Introduction
- •11.2 Modulation of a Sinusoidal Carrier Viewed in the Frequency Domain
- •11.3 Implementation of AM
- •11.3.1 Introduction
- •11.3.2 Some Amplitude Modulation Circuits
- •11.4 Generation of Phase and Frequency Modulation
- •11.4.1 Introduction
- •11.4.3 Integral Pulse Frequency Modulation as a Means of Frequency Modulation
- •11.5 Demodulation of Modulated Sinusoidal Carriers
- •11.5.1 Introduction
- •11.5.2 Detection of AM
- •11.5.3 Detection of FM Signals
- •11.5.4 Demodulation of DSBSCM Signals
- •11.6 Modulation and Demodulation of Digital Carriers
- •11.6.1 Introduction
- •11.6.2 Delta Modulation
- •11.7 Chapter Summary
- •Home Problems
- •12.1 Introduction
- •12.2.1 Introduction
- •12.2.2 The Analog Multiplier/LPF PSR
- •12.2.3 The Switched Op Amp PSR
- •12.2.4 The Chopper PSR
- •12.2.5 The Balanced Diode Bridge PSR
- •12.3 Phase Detectors
- •12.3.1 Introduction
- •12.3.2 The Analog Multiplier Phase Detector
- •12.3.3 Digital Phase Detectors
- •12.4 Voltage and Current-Controlled Oscillators
- •12.4.1 Introduction
- •12.4.2 An Analog VCO
- •12.4.3 Switched Integrating Capacitor VCOs
- •12.4.6 Summary
- •12.5 Phase-Locked Loops
- •12.5.1 Introduction
- •12.5.2 PLL Components
- •12.5.3 PLL Applications in Biomedicine
- •12.5.4 Discussion
- •12.6 True RMS Converters
- •12.6.1 Introduction
- •12.6.2 True RMS Circuits
- •12.7 IC Thermometers
- •12.7.1 Introduction
- •12.7.2 IC Temperature Transducers
- •12.8 Instrumentation Systems
- •12.8.1 Introduction
- •12.8.5 Respiratory Acoustic Impedance Measurement System
- •12.9 Chapter Summary
- •References
292 |
Analysis and Application of Analog Electronic Circuits |
To obtain the symmetric APF, let R1 = R; R5 = 2R4; and R6 = R5. The desired transfer function is then:
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− s R CR R |
+ 1 |
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The natural frequency of poles and zeros is:
ωn = 1/R3C r/s ξ = R/2R2
Kvo = −1, −• ≤ ω ≤ •
(7.36)
(7.37A)
(7.37B)
(7.37C)
The purpose of all-pass filters is to generate a phase shift with frequency with no attenuation; the phase of the APF described earlier can be shown to be:
ϕ = −π − 2 tan |
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7.2.4 Generalized Impedance Converter AFs
Often one wishes to design AFs that work at very low frequencies, e.g., below 20 Hz. Such filters can find application in conditioning low-frequency physiological signals such as the ECG, EEG, and heart sounds. If a conventional biquad AF is used to make a high-pass filter whose fn = 1 Hz, for example, it is necessary to obtain very large capacitors that are expensive and take up excessive volume on a PC board. For example, the capacitor required for fn = 1 Hz and R3 = 100 kΩ is:
C = |
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2 π f R |
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The GIC circuit, shown in general format in Figure 7.8, allows the size of a small capacitor, e.g., 0.001 μF, to be magnified electronically, transformed
into a large, equivalent, very high-Q inductor, or made into a D-element that can be shown to have the impedance, ZD(ω) = 1/(ω2 D), where D is deter-
mined by certain Rs and Cs as shown next.
Find an expression for the driving point impedance of the general GIC circuit, Z11 = V1/I1. Clearly, from Ohm’s law:
V1 |
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Z11 = V1 I1 = (V1 − V2 ) Z1 |
(7.40) |
© 2004 by CRC Press LLC
Analog Active Filters |
293 |
I1
Z1
V1
V2 IOA
Z2 I2
V1
Z3 I3
IOA V3
Z4 I4
V1
Z5 I5
FIGURE 7.8
General architecture for a generalized impedance converter (GIC) circuit. The Zk can be resistances or capacitances (1/jωCk), depending on the filter requirement.
Also, from the ideal op amp assumption and Ohm’s law, it is possible to write the currents:
I2 = (V2 − V1 ) Z2 = I3 = (V1 − V3 ) Z3 |
(7.41) |
I4 = (V3 − V1 ) Z4 = I5 = V1 Z5 |
(7.42) |
From the Equation 7.40, Equation 7.41, and Equation 7.42, it is easy to show:
V3 = V1(1+ Z4 Z5 ) |
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and the GIC driving point impedance is given compactly as:
Z11 = V1/I1 = Z1 Z3 Z5/(Z2 Z4) complex ohms |
(7.45) |
© 2004 by CRC Press LLC
294 |
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Analysis and Application of Analog Electronic Circuits |
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GAIN |
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GICINDUC |
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DB |
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Case = 1 |
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DEG |
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130.00 |
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90.0 |
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104.00 |
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0.0 |
78.00 |
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−90.0 |
52.00 |
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−180.0 |
26.00 |
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−270.0 |
0.00 |
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−360.0 |
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1K |
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10K |
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100K |
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1M |
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100 |
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10M |
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Frequency in Hz |
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Frequency |
= 100.00000E + 05 |
Hz |
Gain |
= 89.003 Db |
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Phase angle = −158.263 |
Degrees |
Group delay = 0.00000E + 00 |
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Gain slope |
= −114.36240E − 01 Db/Oct |
Peak gain |
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1: Another run 2: Analysis limits |
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3: Quit |
4: Dump |
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FIGURE 7.9
Magnitude and phase of Z11(f) looking into a GIC emulation of a 0.1-HY inductor. In this MicroCap simulation, TL072 op amps were used. Smooth line is magnitude.
Now if Z2 or Z4 = 1/jωC (a capacitor) and the other elements are resistors, Z11 has the form:
Z11 = jω [C4 R1R3R5/R2] reactive (inductive) ohms |
(7.46) |
that is, the GIC emulates a low-loss inductor over a wide range of frequency. The inductance of the emulated inductor is:
Leq = [C4 R1R3R5/R2] Hy |
(7.47) |
Figure 7.9 illustrates the magnitude and phase response of an inductive Z11 vs. frequency. Using MicroCap‘, 20 log Z11(f ) and – Z11(f ) vs. f are
plotted. The circuit used in this simulation is the same as in Figure 7.8, with Z1 = Z3 = Z4 = Z5 = 1 kΩ and Z2 = 1/jωC2; C2 = 0.1 μF.
Equation 7.47 shows that the simulated inductance is 0.1 Hy. (Op amp output current saturation effects are not included in this simple simulation.) Note that Z11(f ) increases linearly with frequency until about 180 kHz, at which its phase abruptly goes from the ideal +90 to –270∞, and 20 log Z11(f ) exhibits a tall peak at approximately 1 MHz. Clearly, the circuit model emulates a 0.1-Hy inductor below 180 kHz. A simple nonsaturating, two-time- constant model of the TL082 op amp was used in the MicroCap simulation.
Because the GIC inductive Z11 is referenced to ground, it must be used in active filters that require inductors with one end tied to ground. Figure 7.10(A) illustrates an inductive GIC used in a simple high-Q, quadratic BPF.
© 2004 by CRC Press LLC
Analog Active Filters |
295 |
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IOA |
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R |
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V1 |
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I1 |
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Z11 |
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VS |
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Vo |
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INDUCTOR |
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A
R |
V1 = Vo |
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VS |
Leq |
Vo |
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B
FIGURE 7.10
(A) Circuit of an RLC band-pass filter using the GIC inductor. The GIC circuit allows emulation of a very large, high-Q inductor over a wide range of frequencies and is particularly well suited for making filters in the subaudio range of frequencies. (B) The actual BPF.
Figure 7.10(B) illustrates a simple R–L–C BPF suitable for circuit analysis. A node equation gives the BPF’s transfer function:
V |
(s) = |
sLeq R |
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s2C L |
+ sL R + 1 |
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eq |
eq |
In this filter:
ωn = 1 CLeq rs
Q = 1 (2ξ) = R CLeq
VVo (jωn ) = 1–0∞
S
Leq is given by Equation 7.47.
(7.48)
(7.49A)
(7.49B)
(7.49C)
© 2004 by CRC Press LLC
296 |
Analysis and Application of Analog Electronic Circuits |
R |
V1 |
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D-ELEMENT |
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FIGURE 7.11
Circuit showing how a GIC “D” element can make a low-frequency, low-pass filter.
The GIC “D element” Z11 is a frequency-dependent negative resistance (FDNR) that can be made by putting capacitors in the Z1 and Z3 positions in the GIC circuit. Thus, the driving point impedance is real and negative:
Z |
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(1 jωC1)(1 jωC3 )R5 |
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−R5 |
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−1 |
ohms |
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D = C1C3R2R4 |
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(7.51) |
Figure 7.11 shows that the D element can make a quadratic LPF. Write the node equation for Vo in terms of the Laplace complex variable, s:
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D] = V |
S |
G |
(7.52) |
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Solving for Vo yields: |
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V |
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Clearly, for the GID FDNR LPF, |
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ωn = 1 |
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By using relation Equation 7.44 for V2/VS, it is possible to realize notch and all-pass filters from the basic GIC circuit. Figure 7.12 and Figure 7.13 illustrate examples of these filters. Readers can develop their transfer functions as exercises.
© 2004 by CRC Press LLC