
- •Contents
- •Preface
- •Chapter 1 Introduction (K. Fujimoto)
- •Chapter 2 Small antennas (K. Fujimoto)
- •Chapter 3 Properties of small antennas (K. Fujimoto and Y. Kim)
- •Chapter 4 Fundamental limitation of small antennas (K. Fujimoto)
- •Chapter 5 Subjects related with small antennas (K. Fujimoto)
- •Chapter 6 Principles and techniques for making antennas small (H. Morishita and K. Fujimoto)
- •Chapter 7 Design and practice of small antennas I (K. Fujimoto)
- •Chapter 8 Design and practice of small antennas II (K. Fujimoto)
- •Chapter 9 Evaluation of small antenna performance (H. Morishita)
- •Chapter 10 Electromagnetic simulation (H. Morishita and Y. Kim)
- •Chapter 11 Glossary (K. Fujimoto and N. T. Hung)
- •Acknowledgements
- •1 Introduction
- •2 Small antennas
- •3 Properties of small antennas
- •3.1 Performance of small antennas
- •3.1.1 Input impedance
- •3.1.4 Gain
- •3.2 Importance of impedance matching in small antennas
- •3.3 Problems of environmental effect in small antennas
- •4 Fundamental limitations of small antennas
- •4.1 Fundamental limitations
- •4.2 Brief review of some typical work on small antennas
- •5 Subjects related with small antennas
- •5.1 Major subjects and topics
- •5.1.1 Investigation of fundamentals of small antennas
- •5.1.2 Realization of small antennas
- •5.2 Practical design problems
- •5.3 General topics
- •6 Principles and techniques for making antennas small
- •6.1 Principles for making antennas small
- •6.2 Techniques and methods for producing ESA
- •6.2.1 Lowering the antenna resonance frequency
- •6.2.1.1 SW structure
- •6.2.1.1.1 Periodic structures
- •6.2.1.1.3 Material loading on an antenna structure
- •6.2.2 Full use of volume/space circumscribing antenna
- •6.2.3 Arrangement of current distributions uniformly
- •6.2.4 Increase of radiation modes
- •6.2.4.2 Use of conjugate structure
- •6.2.4.3 Compose with different types of antennas
- •6.2.5 Applications of metamaterials to make antennas small
- •6.2.5.1 Application of SNG to small antennas
- •6.2.5.1.1 Matching in space
- •6.2.5.1.2 Matching at the load terminals
- •6.2.5.2 DNG applications
- •6.3 Techniques and methods to produce FSA
- •6.3.1 FSA composed by integration of components
- •6.3.2 FSA composed by integration of functions
- •6.3.3 FSA of composite structure
- •6.4 Techniques and methods for producing PCSA
- •6.4.2 PCSA employing a high impedance surface
- •6.5 Techniques and methods for making PSA
- •6.5.2 Simple PSA
- •6.6 Optimization techniques
- •6.6.1 Genetic algorithm
- •6.6.2 Particle swarm optimization
- •6.6.3 Topology optimization
- •6.6.4 Volumetric material optimization
- •6.6.5 Practice of optimization
- •6.6.5.1 Outline of particle swarm optimization
- •6.6.5.2 PSO application method and result
- •7 Design and practice of small antennas I
- •7.1 Design and practice
- •7.2 Design and practice of ESA
- •7.2.1 Lowering the resonance frequency
- •7.2.1.1 Use of slow wave structure
- •7.2.1.1.1 Periodic structure
- •7.2.1.1.1.1 Meander line antennas (MLA)
- •7.2.1.1.1.1.1 Dipole-type meander line antenna
- •7.2.1.1.1.1.2 Monopole-type meander line antenna
- •7.2.1.1.1.1.3 Folded-type meander line antenna
- •7.2.1.1.1.1.4 Meander line antenna mounted on a rectangular conducting box
- •7.2.1.1.1.1.5 Small meander line antennas of less than 0.1 wavelength [13]
- •7.2.1.1.1.1.6 MLAs of length L = 0.05 λ [13, 14]
- •7.2.1.1.1.2 Zigzag antennas
- •7.2.1.1.1.3 Normal mode helical antennas (NMHA)
- •7.2.1.1.1.4 Discussions on small NMHA and meander line antennas pertaining to the antenna performances
- •7.2.1.2 Extension of current path
- •7.2.2 Full use of volume/space
- •7.2.2.1.1 Meander line
- •7.2.2.1.4 Spiral antennas
- •7.2.2.1.4.1 Equiangular spiral antenna
- •7.2.2.1.4.2 Archimedean spiral antenna
- •7.2.2.1.4.3.2 Gain
- •7.2.2.1.4.4 Radiation patterns
- •7.2.2.1.4.5 Unidirectional pattern
- •7.2.2.1.4.6 Miniaturization of spiral antenna
- •7.2.2.1.4.6.1 Slot spiral antenna
- •7.2.2.1.4.6.2 Spiral antenna loaded with capacitance
- •7.2.2.1.4.6.3 Archimedean spiral antennas
- •7.2.2.1.4.6.4 Spiral antenna loaded with inductance
- •7.2.2.2 Three-dimensional (3D) structure
- •7.2.2.2.1 Koch trees
- •7.2.2.2.2 3D spiral antenna
- •7.2.2.2.3 Spherical helix
- •7.2.2.2.3.1 Folded semi-spherical monopole antennas
- •7.2.2.2.3.2 Spherical dipole antenna
- •7.2.2.2.3.3 Spherical wire antenna
- •7.2.2.2.3.4 Spherical magnetic (TE mode) dipoles
- •7.2.2.2.3.5 Hemispherical helical antenna
- •7.2.3 Uniform current distribution
- •7.2.3.1 Loading techniques
- •7.2.3.1.1 Monopole with top loading
- •7.2.3.1.2 Cross-T-wire top-loaded monopole with four open sleeves
- •7.2.3.1.3 Slot loaded with spiral
- •7.2.4 Increase of excitation mode
- •7.2.4.1.1 L-shaped quasi-self-complementary antenna
- •7.2.4.1.2 H-shaped quasi-self-complementary antenna
- •7.2.4.1.3 A half-circular disk quasi-self-complementary antenna
- •7.2.4.1.4 Sinuous spiral antenna
- •7.2.4.2 Conjugate structure
- •7.2.4.2.1 Electrically small complementary paired antenna
- •7.2.4.2.2 A combined electric-magnetic type antenna
- •7.2.4.3 Composite structure
- •7.2.4.3.1 Slot-monopole hybrid antenna
- •7.2.4.3.2 Spiral-slots loaded with inductive element
- •7.2.5 Applications of metamaterials
- •7.2.5.1 Applications of SNG (Single Negative) materials
- •7.2.5.1.1.2 Elliptical patch antenna
- •7.2.5.1.1.3 Small loop loaded with CLL
- •7.2.5.1.2 Epsilon-Negative Metamaterials (ENG MM)
- •7.2.5.2 Applications of DNG (Double Negative Materials)
- •7.2.5.2.1 Leaky wave antenna [116]
- •7.2.5.2.3 NRI (Negative Refractive Index) TL MM antennas
- •7.2.6 Active circuit applications to impedance matching
- •7.2.6.1 Antenna matching in transmitter/receiver
- •7.2.6.2 Monopole antenna
- •7.2.6.3 Loop and planar antenna
- •7.2.6.4 Microstrip antenna
- •8 Design and practice of small antennas II
- •8.1 FSA (Functionally Small Antennas)
- •8.1.1 Introduction
- •8.1.2 Integration technique
- •8.1.2.1 Enhancement/improvement of antenna performances
- •8.1.2.1.1 Bandwidth enhancement and multiband operation
- •8.1.2.1.1.1.1 E-shaped microstrip antenna
- •8.1.2.1.1.1.2 -shaped microstrip antenna
- •8.1.2.1.1.1.3 H-shaped microstrip antenna
- •8.1.2.1.1.1.4 S-shaped-slot patch antenna
- •8.1.2.1.1.2.1 Microstrip slot antennas
- •8.1.2.1.1.2.2.2 Rectangular patch with square slot
- •8.1.2.1.2.1.1 A printed λ/8 PIFA operating at penta-band
- •8.1.2.1.2.1.2 Bent-monopole penta-band antenna
- •8.1.2.1.2.1.3 Loop antenna with a U-shaped tuning element for hepta-band operation
- •8.1.2.1.2.1.4 Planar printed strip monopole for eight-band operation
- •8.1.2.1.2.2.2 Folded loop antenna
- •8.1.2.1.2.3.2 Monopole UWB antennas
- •8.1.2.1.2.3.2.1 Binomial-curved patch antenna
- •8.1.2.1.2.3.2.2 Spline-shaped antenna
- •8.1.2.1.2.3.3 UWB antennas with slot/slit embedded on the patch surface
- •8.1.2.1.2.3.3.1 A beveled square monopole patch with U-slot
- •8.1.2.1.2.3.3.2 Circular/Elliptical slot UWB antennas
- •8.1.2.1.2.3.3.3 A rectangular monopole patch with a notch and a strip
- •8.1.2.1.2.3.4.1 Pentagon-shape microstrip slot antenna
- •8.1.2.1.2.3.4.2 Sectorial loop antenna (SLA)
- •8.1.3 Integration of functions into antenna
- •8.2 Design and practice of PCSA (Physically Constrained Small Antennas)
- •8.2.2 Application of HIS (High Impedance Surface)
- •8.2.3 Applications of EBG (Electromagnetic Band Gap)
- •8.2.3.1 Miniaturization
- •8.2.3.2 Enhancement of gain
- •8.2.3.3 Enhancement of bandwidth
- •8.2.3.4 Reduction of mutual coupling
- •8.2.4 Application of DGS (Defected Ground Surface)
- •8.2.4.2 Multiband circular disk monopole patch antenna
- •8.2.5 Application of DBE (Degenerated Band Edge) structure
- •8.3 Design and practice of PSA (Physically Small Antennas)
- •8.3.1 Small antennas for radio watch/clock systems
- •8.3.2 Small antennas for RFID
- •8.3.2.1 Dipole and monopole types
- •8.3.2.3 Slot type antennas
- •8.3.2.4 Loop antenna
- •Appendix I
- •Appendix II
- •References
- •9 Evaluation of small antenna performance
- •9.1 General
- •9.2 Practical method of measurement
- •9.2.1 Measurement by using a coaxial cable
- •9.2.2 Method of measurement by using small oscillator
- •9.2.3 Method of measurement by using optical system
- •9.3 Practice of measurement
- •9.3.1 Input impedance and bandwidth
- •9.3.2 Radiation patterns and gain
- •10 Electromagnetic simulation
- •10.1 Concept of electromagnetic simulation
- •10.2 Typical electromagnetic simulators for small antennas
- •10.3 Example (balanced antennas for mobile handsets)
- •10.3.2 Antenna structure
- •10.3.3 Analytical results
- •10.3.4 Simulation for characteristics of a folded loop antenna in the vicinity of human head and hand
- •10.3.4.1 Structure of human head and hand
- •10.3.4.2 Analytical results
- •11 Glossary
- •11.1 Catalog of small antennas
- •11.2 List of small antennas
- •Index

8.3 Design and practice of PSA |
359 |
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(a)
98 mm
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D1
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Figure 8.116 Circular loop antenna with extended line fed by (a) internal line and (b) external line ([103], copyright C 2006 IEEE).
8.3.2.4Loop antenna
A small circular loop antenna (CLA) operating at 911.25 MHz is designed for application to an RFID tag [103]. A one-wavelength and a half-wavelength CLA with a short stub are fabricated as shown in Figure 8.116, where (a) depicts an antenna with an internal stub, while (b) illustrates an antenna with an outer stub. The antenna dimensions are given in the figure. The stub increases the loop length so that the current path is increased and the diameter of the loop is reduced. The ratios of size reduction compared with a general CLA are 83% and 92%, respectively, for the one-wavelength CLA and the half-wavelength CLA. The return loss, −10 dB bandwidth, and gain are −11.9 dB, 12 MHz (1.3%), and 1.18 dBi, for the one wavelength CLA and −16.5 dB, 48 MHz (5%) and −0.58 dBi, respectively.
Another example is a square loop, but a part of the element is taken out, leaving three corners, as shown in Figure 8.117(a) [104]. Two elements are used to form a quasi-Yagi type antenna, with one element as a driver and another as a reflector, in order to produce a directional pattern as depicted in Figure 8.117(b), and consequent higher gain. The antenna is designed to install in a hand-held RFID reader as illustrated in Figure 8.117(c) for its operation in the near-field environment. The total dimensions of the antenna are 115 × 115 × 13.8 mm for operation of 433.92 MHz. The 10-dB bandwidth is 2.31 MHz (0.53%), covering the required bandwidth of 433.67–434.17 MHz for the ISO/IEC standards. When the reader is held by an operator, the radiation pattern deviates slightly
from the desired direction, the orientation of the reader, because the operators typically hold the reader at a slant. Then, the gain is 2.5 dBi at angle θ = 20◦ (azimuth) at ϕ = 0◦ (elevation), while 2.1 dBi at θ = 0◦.
The antenna radiates circular polarization and the bandwidth in terms of both
impedance and for axial ratio less than 3, is 0.58% (433.23–435.7 MHz) and 1.01% (430.5–434.9 MHz) at θ = 0◦ and 20◦, respectively.

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b: 115 mm (0.166λ) |
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Figure 8.117 A hand-held RFID device loaded with a two-wired broken square loop antenna ([104], copyright C 2010 IEEE).
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Figure 8.A1 A folded dipole [27b].
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Figure 8.A2 Equivalent expression of a folded dipole: (a) balanced mode and (b) unbalanced mode [27b].
Appendix I
By folding an antenna structure, the input impedance depends on the ratio νi of the current distributions on the antenna elements. A folded antenna of length 2L is modeled as depicted in Figure 8A.1 [27b], in which current flows on each element having radius of r1 and r2 are denoted as I1 and I2, respectively, and the driven voltage is V0. This model is equivalently divided into two parts as shown in Figure 8A.2; one is a balanced

8.3 Design and practice of PSA |
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Figure 8.A3 Current distributions at the feed point of the folded dipole connected with a coaxial cable [27b].
mode shown in (a), on which the currents Ib(0) flow on both elements [I(0) : current at the driven terminals] and the driven voltage is Vb. The other part is an unbalanced mode shown in (b), on which current flow on one element is Iu1 = (1 – νi) I(0) and on other element is Iu2 = νi I(0), respectively, and the driven voltage is Vu. Relationships between these voltages are given by
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(A8.1) |
−2νi Vb + Vu = 0 |
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Then, input impedance Zin of the antenna is given by
Zin = V0/[νi Iu (0) + Ib(0)]
= 1/[(Zu /νi ) − 1 + 2Zb − 1] |
(A8.3) |
where Zu = Vu/Iu (0) and Zb = Vb/Ib.
When two elements have the same radius, νi = 1/2.
Appendix II
When a coaxial cable is directly connected to a folded dipole as shown in Figure 8A.3, current I1 flowing into the dipole from the inner conductor of the coax returns to the coax as the sum of the current I2, current at the opposite terminal of the dipole, and I3, current on the outer conductor of the coax, which is equal to the difference of currents I1 and I2 [27b]. This is equivalently rewritten as a model shown in Figure 8A.4(a). This model is further divided into two modes; A and B, respectively, as Figure 8A.4(b) and (c) show. In each mode, the following relationships exist, by

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Figure 8.A4 Current and voltage at the feed point of a folded dipole (a) original mode, (b) and (b ) A mode, and (c) and (c ) B mode [27b].
using Za and Zb, impedances of A mode and B mode, respectively, seen at the terminals b–d,
V0/2 = (I1 |
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(A8.4) |
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(A8.5) |
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When the length of antenna L is a half wavelength, that is, one side is a quarter wavelength, Za becomes infinite, then I1 = I2 = I, and (I1 + I2)/2 = I. This means that the current on the outer conductor of the coax (I1 – I2) disappears, and the same current I flows in and out from the coax, implying that a balun is not required. This is the