- •Contents
- •Preface
- •Chapter 1 Introduction (K. Fujimoto)
- •Chapter 2 Small antennas (K. Fujimoto)
- •Chapter 3 Properties of small antennas (K. Fujimoto and Y. Kim)
- •Chapter 4 Fundamental limitation of small antennas (K. Fujimoto)
- •Chapter 5 Subjects related with small antennas (K. Fujimoto)
- •Chapter 6 Principles and techniques for making antennas small (H. Morishita and K. Fujimoto)
- •Chapter 7 Design and practice of small antennas I (K. Fujimoto)
- •Chapter 8 Design and practice of small antennas II (K. Fujimoto)
- •Chapter 9 Evaluation of small antenna performance (H. Morishita)
- •Chapter 10 Electromagnetic simulation (H. Morishita and Y. Kim)
- •Chapter 11 Glossary (K. Fujimoto and N. T. Hung)
- •Acknowledgements
- •1 Introduction
- •2 Small antennas
- •3 Properties of small antennas
- •3.1 Performance of small antennas
- •3.1.1 Input impedance
- •3.1.4 Gain
- •3.2 Importance of impedance matching in small antennas
- •3.3 Problems of environmental effect in small antennas
- •4 Fundamental limitations of small antennas
- •4.1 Fundamental limitations
- •4.2 Brief review of some typical work on small antennas
- •5 Subjects related with small antennas
- •5.1 Major subjects and topics
- •5.1.1 Investigation of fundamentals of small antennas
- •5.1.2 Realization of small antennas
- •5.2 Practical design problems
- •5.3 General topics
- •6 Principles and techniques for making antennas small
- •6.1 Principles for making antennas small
- •6.2 Techniques and methods for producing ESA
- •6.2.1 Lowering the antenna resonance frequency
- •6.2.1.1 SW structure
- •6.2.1.1.1 Periodic structures
- •6.2.1.1.3 Material loading on an antenna structure
- •6.2.2 Full use of volume/space circumscribing antenna
- •6.2.3 Arrangement of current distributions uniformly
- •6.2.4 Increase of radiation modes
- •6.2.4.2 Use of conjugate structure
- •6.2.4.3 Compose with different types of antennas
- •6.2.5 Applications of metamaterials to make antennas small
- •6.2.5.1 Application of SNG to small antennas
- •6.2.5.1.1 Matching in space
- •6.2.5.1.2 Matching at the load terminals
- •6.2.5.2 DNG applications
- •6.3 Techniques and methods to produce FSA
- •6.3.1 FSA composed by integration of components
- •6.3.2 FSA composed by integration of functions
- •6.3.3 FSA of composite structure
- •6.4 Techniques and methods for producing PCSA
- •6.4.2 PCSA employing a high impedance surface
- •6.5 Techniques and methods for making PSA
- •6.5.2 Simple PSA
- •6.6 Optimization techniques
- •6.6.1 Genetic algorithm
- •6.6.2 Particle swarm optimization
- •6.6.3 Topology optimization
- •6.6.4 Volumetric material optimization
- •6.6.5 Practice of optimization
- •6.6.5.1 Outline of particle swarm optimization
- •6.6.5.2 PSO application method and result
- •7 Design and practice of small antennas I
- •7.1 Design and practice
- •7.2 Design and practice of ESA
- •7.2.1 Lowering the resonance frequency
- •7.2.1.1 Use of slow wave structure
- •7.2.1.1.1 Periodic structure
- •7.2.1.1.1.1 Meander line antennas (MLA)
- •7.2.1.1.1.1.1 Dipole-type meander line antenna
- •7.2.1.1.1.1.2 Monopole-type meander line antenna
- •7.2.1.1.1.1.3 Folded-type meander line antenna
- •7.2.1.1.1.1.4 Meander line antenna mounted on a rectangular conducting box
- •7.2.1.1.1.1.5 Small meander line antennas of less than 0.1 wavelength [13]
- •7.2.1.1.1.1.6 MLAs of length L = 0.05 λ [13, 14]
- •7.2.1.1.1.2 Zigzag antennas
- •7.2.1.1.1.3 Normal mode helical antennas (NMHA)
- •7.2.1.1.1.4 Discussions on small NMHA and meander line antennas pertaining to the antenna performances
- •7.2.1.2 Extension of current path
- •7.2.2 Full use of volume/space
- •7.2.2.1.1 Meander line
- •7.2.2.1.4 Spiral antennas
- •7.2.2.1.4.1 Equiangular spiral antenna
- •7.2.2.1.4.2 Archimedean spiral antenna
- •7.2.2.1.4.3.2 Gain
- •7.2.2.1.4.4 Radiation patterns
- •7.2.2.1.4.5 Unidirectional pattern
- •7.2.2.1.4.6 Miniaturization of spiral antenna
- •7.2.2.1.4.6.1 Slot spiral antenna
- •7.2.2.1.4.6.2 Spiral antenna loaded with capacitance
- •7.2.2.1.4.6.3 Archimedean spiral antennas
- •7.2.2.1.4.6.4 Spiral antenna loaded with inductance
- •7.2.2.2 Three-dimensional (3D) structure
- •7.2.2.2.1 Koch trees
- •7.2.2.2.2 3D spiral antenna
- •7.2.2.2.3 Spherical helix
- •7.2.2.2.3.1 Folded semi-spherical monopole antennas
- •7.2.2.2.3.2 Spherical dipole antenna
- •7.2.2.2.3.3 Spherical wire antenna
- •7.2.2.2.3.4 Spherical magnetic (TE mode) dipoles
- •7.2.2.2.3.5 Hemispherical helical antenna
- •7.2.3 Uniform current distribution
- •7.2.3.1 Loading techniques
- •7.2.3.1.1 Monopole with top loading
- •7.2.3.1.2 Cross-T-wire top-loaded monopole with four open sleeves
- •7.2.3.1.3 Slot loaded with spiral
- •7.2.4 Increase of excitation mode
- •7.2.4.1.1 L-shaped quasi-self-complementary antenna
- •7.2.4.1.2 H-shaped quasi-self-complementary antenna
- •7.2.4.1.3 A half-circular disk quasi-self-complementary antenna
- •7.2.4.1.4 Sinuous spiral antenna
- •7.2.4.2 Conjugate structure
- •7.2.4.2.1 Electrically small complementary paired antenna
- •7.2.4.2.2 A combined electric-magnetic type antenna
- •7.2.4.3 Composite structure
- •7.2.4.3.1 Slot-monopole hybrid antenna
- •7.2.4.3.2 Spiral-slots loaded with inductive element
- •7.2.5 Applications of metamaterials
- •7.2.5.1 Applications of SNG (Single Negative) materials
- •7.2.5.1.1.2 Elliptical patch antenna
- •7.2.5.1.1.3 Small loop loaded with CLL
- •7.2.5.1.2 Epsilon-Negative Metamaterials (ENG MM)
- •7.2.5.2 Applications of DNG (Double Negative Materials)
- •7.2.5.2.1 Leaky wave antenna [116]
- •7.2.5.2.3 NRI (Negative Refractive Index) TL MM antennas
- •7.2.6 Active circuit applications to impedance matching
- •7.2.6.1 Antenna matching in transmitter/receiver
- •7.2.6.2 Monopole antenna
- •7.2.6.3 Loop and planar antenna
- •7.2.6.4 Microstrip antenna
- •8 Design and practice of small antennas II
- •8.1 FSA (Functionally Small Antennas)
- •8.1.1 Introduction
- •8.1.2 Integration technique
- •8.1.2.1 Enhancement/improvement of antenna performances
- •8.1.2.1.1 Bandwidth enhancement and multiband operation
- •8.1.2.1.1.1.1 E-shaped microstrip antenna
- •8.1.2.1.1.1.2 -shaped microstrip antenna
- •8.1.2.1.1.1.3 H-shaped microstrip antenna
- •8.1.2.1.1.1.4 S-shaped-slot patch antenna
- •8.1.2.1.1.2.1 Microstrip slot antennas
- •8.1.2.1.1.2.2.2 Rectangular patch with square slot
- •8.1.2.1.2.1.1 A printed λ/8 PIFA operating at penta-band
- •8.1.2.1.2.1.2 Bent-monopole penta-band antenna
- •8.1.2.1.2.1.3 Loop antenna with a U-shaped tuning element for hepta-band operation
- •8.1.2.1.2.1.4 Planar printed strip monopole for eight-band operation
- •8.1.2.1.2.2.2 Folded loop antenna
- •8.1.2.1.2.3.2 Monopole UWB antennas
- •8.1.2.1.2.3.2.1 Binomial-curved patch antenna
- •8.1.2.1.2.3.2.2 Spline-shaped antenna
- •8.1.2.1.2.3.3 UWB antennas with slot/slit embedded on the patch surface
- •8.1.2.1.2.3.3.1 A beveled square monopole patch with U-slot
- •8.1.2.1.2.3.3.2 Circular/Elliptical slot UWB antennas
- •8.1.2.1.2.3.3.3 A rectangular monopole patch with a notch and a strip
- •8.1.2.1.2.3.4.1 Pentagon-shape microstrip slot antenna
- •8.1.2.1.2.3.4.2 Sectorial loop antenna (SLA)
- •8.1.3 Integration of functions into antenna
- •8.2 Design and practice of PCSA (Physically Constrained Small Antennas)
- •8.2.2 Application of HIS (High Impedance Surface)
- •8.2.3 Applications of EBG (Electromagnetic Band Gap)
- •8.2.3.1 Miniaturization
- •8.2.3.2 Enhancement of gain
- •8.2.3.3 Enhancement of bandwidth
- •8.2.3.4 Reduction of mutual coupling
- •8.2.4 Application of DGS (Defected Ground Surface)
- •8.2.4.2 Multiband circular disk monopole patch antenna
- •8.2.5 Application of DBE (Degenerated Band Edge) structure
- •8.3 Design and practice of PSA (Physically Small Antennas)
- •8.3.1 Small antennas for radio watch/clock systems
- •8.3.2 Small antennas for RFID
- •8.3.2.1 Dipole and monopole types
- •8.3.2.3 Slot type antennas
- •8.3.2.4 Loop antenna
- •Appendix I
- •Appendix II
- •References
- •9 Evaluation of small antenna performance
- •9.1 General
- •9.2 Practical method of measurement
- •9.2.1 Measurement by using a coaxial cable
- •9.2.2 Method of measurement by using small oscillator
- •9.2.3 Method of measurement by using optical system
- •9.3 Practice of measurement
- •9.3.1 Input impedance and bandwidth
- •9.3.2 Radiation patterns and gain
- •10 Electromagnetic simulation
- •10.1 Concept of electromagnetic simulation
- •10.2 Typical electromagnetic simulators for small antennas
- •10.3 Example (balanced antennas for mobile handsets)
- •10.3.2 Antenna structure
- •10.3.3 Analytical results
- •10.3.4 Simulation for characteristics of a folded loop antenna in the vicinity of human head and hand
- •10.3.4.1 Structure of human head and hand
- •10.3.4.2 Analytical results
- •11 Glossary
- •11.1 Catalog of small antennas
- •11.2 List of small antennas
- •Index
7.2 Design and practice of ESA |
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La Ca
Z0 |
ra |
–Ca Ca
Z0 |
ra |
Figure 7.246 Negative capacitance replacing a large inductance in the resonance circuit of a small antenna.
consideration. The operating frequency is 2.45 GHz. Measured results show a resonant frequency of 2.35 GHz with return loss of 23 dB and the –10 dB bandwidth of 4.5%. From the radiation patterns, the gain is evaluated to be 0.16 dBi.
The proposed antenna as fabricated by using small patches and slots could offer fairly good performance with a compact size of λ0/11 square that is very small as compared with a conventional λ0/2 antenna (λ0: free space wavelength).
7.2.6Active circuit applications to impedance matching
An antenna always needs impedance matching in practical use. As was mentioned frequently, matching at the feed terminals of an electrically small antenna is a crucial problem, because of the need to compensate its highly reactive impedance with low loss, and to transform its low resistive impedance to the load impedance (50 ). To overcome this difficulty, two methods have recently been disclosed; one is the use of active circuits and another is matching in the near field of a radiator, instead of matching at the feed terminals. The latter has been described in 6.2.5. Meanwhile, active circuits are applied, for instance, to cancel the large capacitance Ca of a short dipole. In practice, as Figure 7.246 shows, a negative reactance –Ca is used instead of a large inductance La corresponding to the Ca of a short dipole. In the figure, ra denotes the radiation resistance of the dipole. Since La must be large enough to cancel Ca, it may have a large
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Design and practice of small antennas I |
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Zin = –kZL |
NIC |
ZL |
Cin |
C |
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(k > 0) |
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R2 |
R1 |
ZL
–ZL
(b)
NIC
–ZL
Figure 7.247 Negative impedance converter (NIC) and example of practical implementation: (a) grounded type and (b) floating type.
loss that reduces the radiation efficiency, and hence, –Ca substitutes for it. The negative capacitance –Ca can be achieved by a negative reactance circuit, which is constituted of transistors. The negative reactance circuits can be realized by NIC as is illustrated in Figure 7.247, which shows two types of NIC; (a) grounded NIC and (b) floating NIC [126–134]. Examples of transistor circuits are shown on the right-hand side in the figure, where Cin (–C) and –ZL, respectively, are the capacitance converted from C by the grounded NIC and the impedance converted from ZL by the floating NIC.
On the recent advent of NIC application to antennas, antenna engineers have acquired a pragmatic and effective design technique to develop a novel electrically small antenna having high efficiency and possibly wide bandwidth.
Active circuits, which do not follow Foster Reactance Theorem, are referred to as Non-Foster circuits. Another way to obtain proper matching in small antennas is the use of metamaterials (MM), which can represent negative reactance, instead of NIC. An MNG introduced in 7.2.5.1 is a typical example.
It must be noted, when negative reactance circuits are used, that the circuit should maintain stable condition, noise be kept as low as possible, and the linearity be kept as high as possible.
Regarding stability, an NIC needs inevitably to be open-circuit stable (OCS) at one port and short-circuit stable (SCS) at the other port. OCS means that the network is stable for any passive load on one side with the other port open, while SCS means that the network is stable for any passive load on one port with the other port short. The inherent conditional stability of an NIC constrains the magnitude of the impedances that can be connected to the OCS port and to the SCS port. This can be interpreted by the requirements |ZL1| >|Zin1| and |ZL2| < |Zin2|. Figure 7.248(c) illustrates an NIC that has impedances ZL1 and ZL2, respectively, at each load terminal and impedances Zin1 and Zin2 at the input terminals of each side. In designing an NIC circuit, these requirements must always be met.
In addition, there is inconvenience in using the active circuit, as the transistor circuits are generally unidirectional, whereas an antenna is bi-directional, and hence the application is limited to either transmitter or receiver. In addition, transistor circuits need the bias supply, for which additional circuits are required within the antenna system.
7.2 Design and practice of ESA |
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NIC |
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(b) |
NIC |
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(c) ZL1 |
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NIC |
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ZL2 |
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Zin1 |
Zin2 |
Figure 7.248 NIC circuit and stability requirements: (a) shows OCS state, (b) gives SCS state, and
(c) illustrates impedances that concern stability of an NIC; ZL1 ZL2 at the load and Zin1, Zin2 at the input terminals each side.
–L |
–L |
L
Figure 7.249 Impedance transformer between a low resistance and the load (characteristic impedance Zo).
Instead, an NMG material, if it could be available, is greatly advantageous, since the material enables bi-directional application feasibility that is favorable in antenna applications.
Nevertheless, there are distinct advantages of using negative circuits in antenna design, as they can overcome matching difficulty and thus assist in enhancing gain and efficiency in transmitter applications, even when the size of antenna is electrically small, while they may facilitate extension of bandwidth and improvement of signal-to-noise ratio in receiver applications.
NIC may also be used as a circuit that converts low radiation resistance of small antennas to the load (or source) resistance (50 ) after the reactance is compensated. For this purpose, a T-shaped inductance circuit, for example, may be used. Figure 7.249 depicts the circuit, which is formed of a shunt L and two series –Ls. Here, the –L can be produced by an NIC. The matching circuit is then designed to employ NICs, which represent –Ca and –Lm as shown in Figure 7.250.
252 |
Design and practice of small antennas I |
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–L |
–L |
–Ca |
Ca |
L |
ra |
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–Lm |
–Lm |
–Ca |
Ca |
NIC |
NIC |
NIC |
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Lm |
ra |
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Figure 7.250 Matching circuit and impedance transformer using negative reactance.
7.2.6.1Antenna matching in transmitter/receiver
NICs are applied to matching circuits of antennas in the transmitter or the receiver [132, 133]. An example of antenna matching in the transmitter is introduced in [132], which describes a 15–30 MHz band transmitter, for which a two-foot monopole antenna is used. The matching circuit is illustrated in Figure 7.251, where two cases are shown:
(a) passive matching and (b) active matching. In these circuits, an inductance L = 1.8 µH is used for tuning at 20 MHz with the antenna capacitance Ca = 33 pF and a serial L-C circuit, which derives 50 of the load resistance RL from the low resistance 4 at the output stage of the tuning circuit, is used. This 4 at the output of the tuning circuit is attributed to the loss of the inductance L, whereas the radiation resistance of the antenna at 20 MHz is 1 .
In order to transform 1 to the source 50 , a serial L-C network is used as shown in Figure 7.251, which is a different type of circuit to that shown in Figure 7.249.
Meanwhile, in the active matching, a floating NIC, which uses two transistors, each being a pair of npn-pnp, is used to cancel L and Ca, to which the impedance transforming circuit is connected. Then the overall matching circuit will be that as shown in Figure 7.251(b).
The matching characteristics depend on the biasing of the NIC transistors. In [132], the matching characteristics are evaluated by |S21|2, which provides the ratio of the power delivered to the 1 load to the power from the source (50 ), and is compared with that of the passive matching. In the active matching, two biasing cases, that is, conventional class A and class B biasing, are compared.