- •Contents
- •Preface
- •Chapter 1 Introduction (K. Fujimoto)
- •Chapter 2 Small antennas (K. Fujimoto)
- •Chapter 3 Properties of small antennas (K. Fujimoto and Y. Kim)
- •Chapter 4 Fundamental limitation of small antennas (K. Fujimoto)
- •Chapter 5 Subjects related with small antennas (K. Fujimoto)
- •Chapter 6 Principles and techniques for making antennas small (H. Morishita and K. Fujimoto)
- •Chapter 7 Design and practice of small antennas I (K. Fujimoto)
- •Chapter 8 Design and practice of small antennas II (K. Fujimoto)
- •Chapter 9 Evaluation of small antenna performance (H. Morishita)
- •Chapter 10 Electromagnetic simulation (H. Morishita and Y. Kim)
- •Chapter 11 Glossary (K. Fujimoto and N. T. Hung)
- •Acknowledgements
- •1 Introduction
- •2 Small antennas
- •3 Properties of small antennas
- •3.1 Performance of small antennas
- •3.1.1 Input impedance
- •3.1.4 Gain
- •3.2 Importance of impedance matching in small antennas
- •3.3 Problems of environmental effect in small antennas
- •4 Fundamental limitations of small antennas
- •4.1 Fundamental limitations
- •4.2 Brief review of some typical work on small antennas
- •5 Subjects related with small antennas
- •5.1 Major subjects and topics
- •5.1.1 Investigation of fundamentals of small antennas
- •5.1.2 Realization of small antennas
- •5.2 Practical design problems
- •5.3 General topics
- •6 Principles and techniques for making antennas small
- •6.1 Principles for making antennas small
- •6.2 Techniques and methods for producing ESA
- •6.2.1 Lowering the antenna resonance frequency
- •6.2.1.1 SW structure
- •6.2.1.1.1 Periodic structures
- •6.2.1.1.3 Material loading on an antenna structure
- •6.2.2 Full use of volume/space circumscribing antenna
- •6.2.3 Arrangement of current distributions uniformly
- •6.2.4 Increase of radiation modes
- •6.2.4.2 Use of conjugate structure
- •6.2.4.3 Compose with different types of antennas
- •6.2.5 Applications of metamaterials to make antennas small
- •6.2.5.1 Application of SNG to small antennas
- •6.2.5.1.1 Matching in space
- •6.2.5.1.2 Matching at the load terminals
- •6.2.5.2 DNG applications
- •6.3 Techniques and methods to produce FSA
- •6.3.1 FSA composed by integration of components
- •6.3.2 FSA composed by integration of functions
- •6.3.3 FSA of composite structure
- •6.4 Techniques and methods for producing PCSA
- •6.4.2 PCSA employing a high impedance surface
- •6.5 Techniques and methods for making PSA
- •6.5.2 Simple PSA
- •6.6 Optimization techniques
- •6.6.1 Genetic algorithm
- •6.6.2 Particle swarm optimization
- •6.6.3 Topology optimization
- •6.6.4 Volumetric material optimization
- •6.6.5 Practice of optimization
- •6.6.5.1 Outline of particle swarm optimization
- •6.6.5.2 PSO application method and result
- •7 Design and practice of small antennas I
- •7.1 Design and practice
- •7.2 Design and practice of ESA
- •7.2.1 Lowering the resonance frequency
- •7.2.1.1 Use of slow wave structure
- •7.2.1.1.1 Periodic structure
- •7.2.1.1.1.1 Meander line antennas (MLA)
- •7.2.1.1.1.1.1 Dipole-type meander line antenna
- •7.2.1.1.1.1.2 Monopole-type meander line antenna
- •7.2.1.1.1.1.3 Folded-type meander line antenna
- •7.2.1.1.1.1.4 Meander line antenna mounted on a rectangular conducting box
- •7.2.1.1.1.1.5 Small meander line antennas of less than 0.1 wavelength [13]
- •7.2.1.1.1.1.6 MLAs of length L = 0.05 λ [13, 14]
- •7.2.1.1.1.2 Zigzag antennas
- •7.2.1.1.1.3 Normal mode helical antennas (NMHA)
- •7.2.1.1.1.4 Discussions on small NMHA and meander line antennas pertaining to the antenna performances
- •7.2.1.2 Extension of current path
- •7.2.2 Full use of volume/space
- •7.2.2.1.1 Meander line
- •7.2.2.1.4 Spiral antennas
- •7.2.2.1.4.1 Equiangular spiral antenna
- •7.2.2.1.4.2 Archimedean spiral antenna
- •7.2.2.1.4.3.2 Gain
- •7.2.2.1.4.4 Radiation patterns
- •7.2.2.1.4.5 Unidirectional pattern
- •7.2.2.1.4.6 Miniaturization of spiral antenna
- •7.2.2.1.4.6.1 Slot spiral antenna
- •7.2.2.1.4.6.2 Spiral antenna loaded with capacitance
- •7.2.2.1.4.6.3 Archimedean spiral antennas
- •7.2.2.1.4.6.4 Spiral antenna loaded with inductance
- •7.2.2.2 Three-dimensional (3D) structure
- •7.2.2.2.1 Koch trees
- •7.2.2.2.2 3D spiral antenna
- •7.2.2.2.3 Spherical helix
- •7.2.2.2.3.1 Folded semi-spherical monopole antennas
- •7.2.2.2.3.2 Spherical dipole antenna
- •7.2.2.2.3.3 Spherical wire antenna
- •7.2.2.2.3.4 Spherical magnetic (TE mode) dipoles
- •7.2.2.2.3.5 Hemispherical helical antenna
- •7.2.3 Uniform current distribution
- •7.2.3.1 Loading techniques
- •7.2.3.1.1 Monopole with top loading
- •7.2.3.1.2 Cross-T-wire top-loaded monopole with four open sleeves
- •7.2.3.1.3 Slot loaded with spiral
- •7.2.4 Increase of excitation mode
- •7.2.4.1.1 L-shaped quasi-self-complementary antenna
- •7.2.4.1.2 H-shaped quasi-self-complementary antenna
- •7.2.4.1.3 A half-circular disk quasi-self-complementary antenna
- •7.2.4.1.4 Sinuous spiral antenna
- •7.2.4.2 Conjugate structure
- •7.2.4.2.1 Electrically small complementary paired antenna
- •7.2.4.2.2 A combined electric-magnetic type antenna
- •7.2.4.3 Composite structure
- •7.2.4.3.1 Slot-monopole hybrid antenna
- •7.2.4.3.2 Spiral-slots loaded with inductive element
- •7.2.5 Applications of metamaterials
- •7.2.5.1 Applications of SNG (Single Negative) materials
- •7.2.5.1.1.2 Elliptical patch antenna
- •7.2.5.1.1.3 Small loop loaded with CLL
- •7.2.5.1.2 Epsilon-Negative Metamaterials (ENG MM)
- •7.2.5.2 Applications of DNG (Double Negative Materials)
- •7.2.5.2.1 Leaky wave antenna [116]
- •7.2.5.2.3 NRI (Negative Refractive Index) TL MM antennas
- •7.2.6 Active circuit applications to impedance matching
- •7.2.6.1 Antenna matching in transmitter/receiver
- •7.2.6.2 Monopole antenna
- •7.2.6.3 Loop and planar antenna
- •7.2.6.4 Microstrip antenna
- •8 Design and practice of small antennas II
- •8.1 FSA (Functionally Small Antennas)
- •8.1.1 Introduction
- •8.1.2 Integration technique
- •8.1.2.1 Enhancement/improvement of antenna performances
- •8.1.2.1.1 Bandwidth enhancement and multiband operation
- •8.1.2.1.1.1.1 E-shaped microstrip antenna
- •8.1.2.1.1.1.2 -shaped microstrip antenna
- •8.1.2.1.1.1.3 H-shaped microstrip antenna
- •8.1.2.1.1.1.4 S-shaped-slot patch antenna
- •8.1.2.1.1.2.1 Microstrip slot antennas
- •8.1.2.1.1.2.2.2 Rectangular patch with square slot
- •8.1.2.1.2.1.1 A printed λ/8 PIFA operating at penta-band
- •8.1.2.1.2.1.2 Bent-monopole penta-band antenna
- •8.1.2.1.2.1.3 Loop antenna with a U-shaped tuning element for hepta-band operation
- •8.1.2.1.2.1.4 Planar printed strip monopole for eight-band operation
- •8.1.2.1.2.2.2 Folded loop antenna
- •8.1.2.1.2.3.2 Monopole UWB antennas
- •8.1.2.1.2.3.2.1 Binomial-curved patch antenna
- •8.1.2.1.2.3.2.2 Spline-shaped antenna
- •8.1.2.1.2.3.3 UWB antennas with slot/slit embedded on the patch surface
- •8.1.2.1.2.3.3.1 A beveled square monopole patch with U-slot
- •8.1.2.1.2.3.3.2 Circular/Elliptical slot UWB antennas
- •8.1.2.1.2.3.3.3 A rectangular monopole patch with a notch and a strip
- •8.1.2.1.2.3.4.1 Pentagon-shape microstrip slot antenna
- •8.1.2.1.2.3.4.2 Sectorial loop antenna (SLA)
- •8.1.3 Integration of functions into antenna
- •8.2 Design and practice of PCSA (Physically Constrained Small Antennas)
- •8.2.2 Application of HIS (High Impedance Surface)
- •8.2.3 Applications of EBG (Electromagnetic Band Gap)
- •8.2.3.1 Miniaturization
- •8.2.3.2 Enhancement of gain
- •8.2.3.3 Enhancement of bandwidth
- •8.2.3.4 Reduction of mutual coupling
- •8.2.4 Application of DGS (Defected Ground Surface)
- •8.2.4.2 Multiband circular disk monopole patch antenna
- •8.2.5 Application of DBE (Degenerated Band Edge) structure
- •8.3 Design and practice of PSA (Physically Small Antennas)
- •8.3.1 Small antennas for radio watch/clock systems
- •8.3.2 Small antennas for RFID
- •8.3.2.1 Dipole and monopole types
- •8.3.2.3 Slot type antennas
- •8.3.2.4 Loop antenna
- •Appendix I
- •Appendix II
- •References
- •9 Evaluation of small antenna performance
- •9.1 General
- •9.2 Practical method of measurement
- •9.2.1 Measurement by using a coaxial cable
- •9.2.2 Method of measurement by using small oscillator
- •9.2.3 Method of measurement by using optical system
- •9.3 Practice of measurement
- •9.3.1 Input impedance and bandwidth
- •9.3.2 Radiation patterns and gain
- •10 Electromagnetic simulation
- •10.1 Concept of electromagnetic simulation
- •10.2 Typical electromagnetic simulators for small antennas
- •10.3 Example (balanced antennas for mobile handsets)
- •10.3.2 Antenna structure
- •10.3.3 Analytical results
- •10.3.4 Simulation for characteristics of a folded loop antenna in the vicinity of human head and hand
- •10.3.4.1 Structure of human head and hand
- •10.3.4.2 Analytical results
- •11 Glossary
- •11.1 Catalog of small antennas
- •11.2 List of small antennas
- •Index
200 |
Design and practice of small antennas I |
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Top-load
Open-sleeve element
Driven monopole
Ground
Figure 7.176 Geometry of the cross-T line loaded antenna with sleeves ([85], copyright C 2006 IEEE).
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0 |
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(dB)loss |
−5 |
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−10 |
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Return |
−15 |
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−20 |
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−25 |
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Without sleeve elements |
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With sleeve elements |
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−30 |
120 |
160 |
200 |
240 |
280 |
320 |
360 |
400 |
440 |
480 |
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80 |
Frequency (GHz)
Figure 7.177 Return-loss characteristics ([85], copyright C 2006 IEEE).
and spherical-cap dipole, respectively, for the resonance frequency of near 300 MHz. Antennas were matched to the load of 50 by using a shunt stub at the feed point.
7.2.3.1.2 Cross-T-wire top-loaded monopole with four open sleeves
The antenna configuration is illustrated in Figure 7.176 [85]. The ground plane is assumed to be infinite. The geometrical dimensions of the antenna are: length of driven element L0 = 0.13λ0, length of the top-load element L1 = 0.035λ0, length of sleeve L2 = 0.1λ0, wire diameter a = 0.015λ0, and distance between the driven element and the sleeve R = 0.049λ0, where λ0 is the wavelength at the resonance that is 100 MHz. Return loss is depicted in Figure 7.177 and its variation for different length L2 of the sleeves is shown in Figure 7.178, where L2/λ0 is varied from 0.110 (case 1-1), 0.0105 (case 1-2), 0.095 (case 1-3), and 0.09 (case 1-4). The figure shows that decreasing the length L2 of the sleeves increases the bandwidth.
7.2 Design and practice of ESA |
201 |
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Return loss (dB)
0
−5
−10
−15
−20 |
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Case1-1 |
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−25 |
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Case1-2 |
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Case1-3 |
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Case1-4 |
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−30 |
120 |
160 |
200 |
240 |
280 |
80 |
Frequency (MHz)
Figure 7.178 Variation of return loss depending on the length of the sleeve ([85], copyright C 2006
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IEEE). |
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2 |
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3 |
75 Ω |
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2 |
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Slot antennas |
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1 |
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75 Ω |
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1 |
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(cm)y |
0 |
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(cm)y |
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−1 |
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Feed point |
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−1 |
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Slot antenna |
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−2 |
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−2 |
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Feed point |
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−3 |
−2 |
50 Ω |
0 |
1 |
2 |
3 |
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−3 |
50 Ω |
−4 |
−3 |
−2 |
−1 |
0 |
1 |
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−3 |
−1 |
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−6 |
−5 |
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x (cm) |
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x (cm) |
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(a) |
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(b) |
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Figure 7.179 (a) Geometry of single-element miniaturized slot antenna (SEA) and (b) geometry of double-element miniaturized slot antenna (DEA) ([87]).
7.2.3.1.3 Slot loaded with spiral
As a different type of small-sized loaded antenna, a slot antenna terminated with spiral elements is introduced in [86] (Figure 7.179(a)). The radiating slot is designed to have length λg/4 and is terminated with two identical quarter-wavelength non-radiating spiral slots. λg is the wavelength of the quasi-TEM mode supported by the slot line. In principle, as a resonant quarter-wavelength transmission line exhibits a short at one end reflected to an open at the other end, the non-radiating quarter-wavelength spiral slot shorted at one end behaves as an open at the other end. Therefore, a quarter-wavelength slot line shorted at one end and terminated by the non-radiating quarter-wavelength spiral should resonate and radiate the electromagnetic wave very efficiently. With this configuration,
202Design and practice of small antennas I
the antenna is reduced in size by half, and further reduction is accomplished by bending the radiating slot line. The antenna geometry along with dimensions is illustrated in Figure 7.179(a). The antenna occupies an area of about 0.15λ0 × 0.13λ0.
Since this antenna exhibits very narrow bandwidth, less than 1%, another parasitic antenna with the same configuration is placed in the remaining area in order to increase the bandwidth without significantly increasing the overall PCB (printed circuit board) size, as Figure 7.179(b) illustrates [87]. One of these two antennas is fed by a microstrip line, leaving the other one as a parasitic antenna. The parasitic antenna is coupled with the radiating slot at the elbow section, where the electric field is large. The magnetic currents on each antenna are in phase, so the radiation is enhanced. The two antennas are designed to resonate at the same frequency fr1 = fr2 = f0, where fr1 and fr2 are the resonance frequencies of each antenna, and f0 is the center frequency. In this antenna system, S11, spectral response of the two coupled antennas, exhibits two nulls, as the coupling is adjusted strong enough to increase the bandwidth compared with that of a single slot antenna. The separation of these two frequencies is a function of the separation s and distance d of the overlapped elbow section of these two antennas. The coupling kt between these two antennas is defined as,
kt = ( fu2 − fl2)/( fu2 + fl2) |
(7.71) |
where fu and fl, respectively, are the frequencies of the upper and lower nulls in S11. The kt can be adjusted by varying s and d, increasing with decrease in s and increase in d. The designed resonance frequency fr1 = fr2 = 850 MHz; however, slightly different frequencies can be used to achieve a higher degree of control for tuning response. The input impedance of this antenna, for a given slot width, depends on the location of the microstrip line feed relative to one end of the slot and varies from zero at the short circuited end to a high resistance at the center. The optimum feed position can be observed in Figure 7.179(b), which shows the feed line, consisting of a 50transmission line connected to an open-circuited 75transmission line, which crosses the slot. The 75line is extended by 0.33λm beyond the strip-slot crossing to couple the maximum energy to the slot and also to compensate for the imaginary part of the input impedance (λm: wavelength of the wave in the strip line).
Antennas, two single-element antennas (SEA1 and SEA2) and a double-element antenna (DEA) (Figure 7.179(a) and (b)), are fabricated on a substrate of thickness 500 µm, having a dielectric constant of εr = 3.5 and a loss tangent of tan δ = 0.003, with a copper ground plane of 33.5 mm × 23 mm. The SEA1 is the constitutive element of the DEA and the SEA2 is an SEA having the same topology as the SEA1. Both calculated and measured S11 of the DEA and the SEA2 are shown in Figure 7.180, which indicates bandwidth of 21.6 MHz (2.54%) in the DEA, being wider than 8 MHz (0.9%) of the SEA1 and 11.7 MHz (1.31%) of the SEA2. The measured gain of the DEA is 1.7 dB at 852 MHz, which is greater than that of the SEA1 of approximately 0.8 dB at 850 MHz. The antenna size of the SEA1 is 0.133λ0 × 0.154λ0, while that of the SEA2 and the DEA is 0.165λ0 × 0.157λ0.
By adding series inductive elements to a slot antenna, the size of the antenna can be further reduced. A dual-band small antenna is also developed by adjusting the coupling factor kt so as to create two separate frequencies in the S11 response [87].