- •Contents
- •Preface
- •Chapter 1 Introduction (K. Fujimoto)
- •Chapter 2 Small antennas (K. Fujimoto)
- •Chapter 3 Properties of small antennas (K. Fujimoto and Y. Kim)
- •Chapter 4 Fundamental limitation of small antennas (K. Fujimoto)
- •Chapter 5 Subjects related with small antennas (K. Fujimoto)
- •Chapter 6 Principles and techniques for making antennas small (H. Morishita and K. Fujimoto)
- •Chapter 7 Design and practice of small antennas I (K. Fujimoto)
- •Chapter 8 Design and practice of small antennas II (K. Fujimoto)
- •Chapter 9 Evaluation of small antenna performance (H. Morishita)
- •Chapter 10 Electromagnetic simulation (H. Morishita and Y. Kim)
- •Chapter 11 Glossary (K. Fujimoto and N. T. Hung)
- •Acknowledgements
- •1 Introduction
- •2 Small antennas
- •3 Properties of small antennas
- •3.1 Performance of small antennas
- •3.1.1 Input impedance
- •3.1.4 Gain
- •3.2 Importance of impedance matching in small antennas
- •3.3 Problems of environmental effect in small antennas
- •4 Fundamental limitations of small antennas
- •4.1 Fundamental limitations
- •4.2 Brief review of some typical work on small antennas
- •5 Subjects related with small antennas
- •5.1 Major subjects and topics
- •5.1.1 Investigation of fundamentals of small antennas
- •5.1.2 Realization of small antennas
- •5.2 Practical design problems
- •5.3 General topics
- •6 Principles and techniques for making antennas small
- •6.1 Principles for making antennas small
- •6.2 Techniques and methods for producing ESA
- •6.2.1 Lowering the antenna resonance frequency
- •6.2.1.1 SW structure
- •6.2.1.1.1 Periodic structures
- •6.2.1.1.3 Material loading on an antenna structure
- •6.2.2 Full use of volume/space circumscribing antenna
- •6.2.3 Arrangement of current distributions uniformly
- •6.2.4 Increase of radiation modes
- •6.2.4.2 Use of conjugate structure
- •6.2.4.3 Compose with different types of antennas
- •6.2.5 Applications of metamaterials to make antennas small
- •6.2.5.1 Application of SNG to small antennas
- •6.2.5.1.1 Matching in space
- •6.2.5.1.2 Matching at the load terminals
- •6.2.5.2 DNG applications
- •6.3 Techniques and methods to produce FSA
- •6.3.1 FSA composed by integration of components
- •6.3.2 FSA composed by integration of functions
- •6.3.3 FSA of composite structure
- •6.4 Techniques and methods for producing PCSA
- •6.4.2 PCSA employing a high impedance surface
- •6.5 Techniques and methods for making PSA
- •6.5.2 Simple PSA
- •6.6 Optimization techniques
- •6.6.1 Genetic algorithm
- •6.6.2 Particle swarm optimization
- •6.6.3 Topology optimization
- •6.6.4 Volumetric material optimization
- •6.6.5 Practice of optimization
- •6.6.5.1 Outline of particle swarm optimization
- •6.6.5.2 PSO application method and result
- •7 Design and practice of small antennas I
- •7.1 Design and practice
- •7.2 Design and practice of ESA
- •7.2.1 Lowering the resonance frequency
- •7.2.1.1 Use of slow wave structure
- •7.2.1.1.1 Periodic structure
- •7.2.1.1.1.1 Meander line antennas (MLA)
- •7.2.1.1.1.1.1 Dipole-type meander line antenna
- •7.2.1.1.1.1.2 Monopole-type meander line antenna
- •7.2.1.1.1.1.3 Folded-type meander line antenna
- •7.2.1.1.1.1.4 Meander line antenna mounted on a rectangular conducting box
- •7.2.1.1.1.1.5 Small meander line antennas of less than 0.1 wavelength [13]
- •7.2.1.1.1.1.6 MLAs of length L = 0.05 λ [13, 14]
- •7.2.1.1.1.2 Zigzag antennas
- •7.2.1.1.1.3 Normal mode helical antennas (NMHA)
- •7.2.1.1.1.4 Discussions on small NMHA and meander line antennas pertaining to the antenna performances
- •7.2.1.2 Extension of current path
- •7.2.2 Full use of volume/space
- •7.2.2.1.1 Meander line
- •7.2.2.1.4 Spiral antennas
- •7.2.2.1.4.1 Equiangular spiral antenna
- •7.2.2.1.4.2 Archimedean spiral antenna
- •7.2.2.1.4.3.2 Gain
- •7.2.2.1.4.4 Radiation patterns
- •7.2.2.1.4.5 Unidirectional pattern
- •7.2.2.1.4.6 Miniaturization of spiral antenna
- •7.2.2.1.4.6.1 Slot spiral antenna
- •7.2.2.1.4.6.2 Spiral antenna loaded with capacitance
- •7.2.2.1.4.6.3 Archimedean spiral antennas
- •7.2.2.1.4.6.4 Spiral antenna loaded with inductance
- •7.2.2.2 Three-dimensional (3D) structure
- •7.2.2.2.1 Koch trees
- •7.2.2.2.2 3D spiral antenna
- •7.2.2.2.3 Spherical helix
- •7.2.2.2.3.1 Folded semi-spherical monopole antennas
- •7.2.2.2.3.2 Spherical dipole antenna
- •7.2.2.2.3.3 Spherical wire antenna
- •7.2.2.2.3.4 Spherical magnetic (TE mode) dipoles
- •7.2.2.2.3.5 Hemispherical helical antenna
- •7.2.3 Uniform current distribution
- •7.2.3.1 Loading techniques
- •7.2.3.1.1 Monopole with top loading
- •7.2.3.1.2 Cross-T-wire top-loaded monopole with four open sleeves
- •7.2.3.1.3 Slot loaded with spiral
- •7.2.4 Increase of excitation mode
- •7.2.4.1.1 L-shaped quasi-self-complementary antenna
- •7.2.4.1.2 H-shaped quasi-self-complementary antenna
- •7.2.4.1.3 A half-circular disk quasi-self-complementary antenna
- •7.2.4.1.4 Sinuous spiral antenna
- •7.2.4.2 Conjugate structure
- •7.2.4.2.1 Electrically small complementary paired antenna
- •7.2.4.2.2 A combined electric-magnetic type antenna
- •7.2.4.3 Composite structure
- •7.2.4.3.1 Slot-monopole hybrid antenna
- •7.2.4.3.2 Spiral-slots loaded with inductive element
- •7.2.5 Applications of metamaterials
- •7.2.5.1 Applications of SNG (Single Negative) materials
- •7.2.5.1.1.2 Elliptical patch antenna
- •7.2.5.1.1.3 Small loop loaded with CLL
- •7.2.5.1.2 Epsilon-Negative Metamaterials (ENG MM)
- •7.2.5.2 Applications of DNG (Double Negative Materials)
- •7.2.5.2.1 Leaky wave antenna [116]
- •7.2.5.2.3 NRI (Negative Refractive Index) TL MM antennas
- •7.2.6 Active circuit applications to impedance matching
- •7.2.6.1 Antenna matching in transmitter/receiver
- •7.2.6.2 Monopole antenna
- •7.2.6.3 Loop and planar antenna
- •7.2.6.4 Microstrip antenna
- •8 Design and practice of small antennas II
- •8.1 FSA (Functionally Small Antennas)
- •8.1.1 Introduction
- •8.1.2 Integration technique
- •8.1.2.1 Enhancement/improvement of antenna performances
- •8.1.2.1.1 Bandwidth enhancement and multiband operation
- •8.1.2.1.1.1.1 E-shaped microstrip antenna
- •8.1.2.1.1.1.2 -shaped microstrip antenna
- •8.1.2.1.1.1.3 H-shaped microstrip antenna
- •8.1.2.1.1.1.4 S-shaped-slot patch antenna
- •8.1.2.1.1.2.1 Microstrip slot antennas
- •8.1.2.1.1.2.2.2 Rectangular patch with square slot
- •8.1.2.1.2.1.1 A printed λ/8 PIFA operating at penta-band
- •8.1.2.1.2.1.2 Bent-monopole penta-band antenna
- •8.1.2.1.2.1.3 Loop antenna with a U-shaped tuning element for hepta-band operation
- •8.1.2.1.2.1.4 Planar printed strip monopole for eight-band operation
- •8.1.2.1.2.2.2 Folded loop antenna
- •8.1.2.1.2.3.2 Monopole UWB antennas
- •8.1.2.1.2.3.2.1 Binomial-curved patch antenna
- •8.1.2.1.2.3.2.2 Spline-shaped antenna
- •8.1.2.1.2.3.3 UWB antennas with slot/slit embedded on the patch surface
- •8.1.2.1.2.3.3.1 A beveled square monopole patch with U-slot
- •8.1.2.1.2.3.3.2 Circular/Elliptical slot UWB antennas
- •8.1.2.1.2.3.3.3 A rectangular monopole patch with a notch and a strip
- •8.1.2.1.2.3.4.1 Pentagon-shape microstrip slot antenna
- •8.1.2.1.2.3.4.2 Sectorial loop antenna (SLA)
- •8.1.3 Integration of functions into antenna
- •8.2 Design and practice of PCSA (Physically Constrained Small Antennas)
- •8.2.2 Application of HIS (High Impedance Surface)
- •8.2.3 Applications of EBG (Electromagnetic Band Gap)
- •8.2.3.1 Miniaturization
- •8.2.3.2 Enhancement of gain
- •8.2.3.3 Enhancement of bandwidth
- •8.2.3.4 Reduction of mutual coupling
- •8.2.4 Application of DGS (Defected Ground Surface)
- •8.2.4.2 Multiband circular disk monopole patch antenna
- •8.2.5 Application of DBE (Degenerated Band Edge) structure
- •8.3 Design and practice of PSA (Physically Small Antennas)
- •8.3.1 Small antennas for radio watch/clock systems
- •8.3.2 Small antennas for RFID
- •8.3.2.1 Dipole and monopole types
- •8.3.2.3 Slot type antennas
- •8.3.2.4 Loop antenna
- •Appendix I
- •Appendix II
- •References
- •9 Evaluation of small antenna performance
- •9.1 General
- •9.2 Practical method of measurement
- •9.2.1 Measurement by using a coaxial cable
- •9.2.2 Method of measurement by using small oscillator
- •9.2.3 Method of measurement by using optical system
- •9.3 Practice of measurement
- •9.3.1 Input impedance and bandwidth
- •9.3.2 Radiation patterns and gain
- •10 Electromagnetic simulation
- •10.1 Concept of electromagnetic simulation
- •10.2 Typical electromagnetic simulators for small antennas
- •10.3 Example (balanced antennas for mobile handsets)
- •10.3.2 Antenna structure
- •10.3.3 Analytical results
- •10.3.4 Simulation for characteristics of a folded loop antenna in the vicinity of human head and hand
- •10.3.4.1 Structure of human head and hand
- •10.3.4.2 Analytical results
- •11 Glossary
- •11.1 Catalog of small antennas
- •11.2 List of small antennas
- •Index
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Design and practice of small antennas I |
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Figure 7.202 Photograph of fabricated CBCSLA ([100], copyright C 2008 IEEE).
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Figure 7.203 Topology of cavity-backed slot loop antenna; (a) original slot loop, (b) modified slot loop for size reduction, and (c) sectionalized slot loop for input impedance matching ([100], copyright C 2008 IEEE).
the geometry shows conceptually the proposed composite slot loop antenna, which is fed capacitively with a stub. To reduce the antenna dimensions, the edges of each slot are folded into a spiral-like shape that acts at the same time as inductive load on the edges. Figure 7.204 shows the antenna structure along with the antenna geometrical parameters. As can be seen in the figure, the coax feed is connected to the six Coplanar Waveguides (CPW), by which each of the slots is fed separately. At the edges of each CPW line, a corrugated stub is attached to control capacitance and thus improve impedance matching to the slot. Measured and simulated S11 of the CBCSLA with the cavity height hc = 12.7 mm is shown in Figure 7.205, and simulated radiation pattern is depicted in Figure 7.206.
7.2.5Applications of metamaterials
Real metamaterials (MM) are not available in nature; however, equivalent media may be constructed of either resonant particles (RP) MM [101a, b, 102] or transmission lines (TL) MM [103a, b]. The RP MM may consist of periodical arrays of sub-wavelength thin wires (Figure 6.18) [101] or split rings (Figure 6.19) [102]. They provide either negative
7.2 Design and practice of ESA |
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Figure 7.204 Topology of the reduced-size CBCSLA and corrugated capacitive stub ([100], copyright C 2008 IEEE).
S11 (dB)
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Figure 7.205 Measured and simulated S11 of the reduced-size CBCSLA with hc = 12.7 mm. ([100], copyright C 2008 IEEE).
permittivity or permeability within their restricted frequency range, and a combination of them leads to a double negative medium (DNG). The TL MM may contain composite RH/LH transmission lines (CRLH TL) [103], which are obtained by cascading a sub-wavelength unit cell constituted of a series capacitance and a shunt inductance as the LH MM structure, and unavoidable parasitic shunt capacitance and series inductance existing in the practical circuit implementation as the RH MM structure. The RP
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Design and practice of small antennas I |
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Figure 7.206 Simulated radiation pattern of reduced-size CBCSLA ([100], copyright C 2008 IEEE).
MM has unfavorable properties; the typical ones are unsuitability for most microwave applications, narrow bandwidth, large loss, and necessity of volumetric formation. The TL MM, on the contrary, has advantages: applicability in microwave frequency regions, wide bandwidth, low loss, and suitability for implementing in not only planar, but also volumetric structures. They have been extensively studied, and various applications to electromagnetic devices and antennas have been introduced [104–106].
The MM has unique dispersive characteristics and phase delay of wave propagation in the media that are attributes of double negative constitutive parameters (ε < 0, μ < 0). These MM properties can be effectively used to develop novel antennas. In the CRLH MM, as the frequency ω becomes higher, the wave number β decreases, corresponding to increase in the wavelength λ, thus lowering the resonance frequency in the media. Hence, an appropriate design of the wave number β in an antenna system constituted of an LH medium to obtain desired frequency ω renders the antenna size reduction.
In a CRLH TL MM of length l, constituted of a finite number N multiple unit cells of length p, there would exist multiple resonance modes when length l is a multiple of half a wavelength λg (guided wavelength), that is, l = nλg/2, with n = 0, ± 1, ±2, . . . ± ∞. A CRLH TL can be treated as effectively homogeneous media when the electrical length of the unit cell is smaller than π /2, that is, p < λg/4. The dispersion diagram of the CRLH TL MM is shown in Figure 7.207. The CRLH structure can support negative resonance (n < 0) in the LH region, because of transfer of the phase origin from frequency zero to the transition frequency ω0, and also zeroth-order resonance (n = 0) at ω0 in addition to the ordinary positive resonance (n > 0) in the RH region [107] (Figure 7.207 and Figure 6.49). Multiple resonances may occur at frequencies of n π /N. Therefore, resonance at two or more frequencies in a medium can be attained, indicating possibility of a multiband antenna design. When n = 0, that is the zero-order mode, β = 0, and λ is infinite, but the group velocity vg is not zero, as the wavelength becomes infinite, and the amplitude and phase of the wave are the same anywhere in the media. This means that the resonance is not dependent on the dimensions of the resonator, but
7.2 Design and practice of ESA |
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Figure 7.207 Resonance spectrum of a CRLH structure ([116], copyright C 2008 IEEE).
solely on the values of lumped reactive components on the unit cells, and hence this property can be exploited to design an electrically small antenna.
In the DNG media, negative β (the wave number) suggests that direction of the power propagation in the media is opposite to that of the phase propagation. By introducing such condition as negative β in an antenna structure, a backward radiation can easily be produced, whereas an ordinary LW (Leaky Wave) antenna radiates only in the forward direction. A balanced-type CRLH TL [103a] can be used for a frequency scanned LW antenna, which is designed to produce backward radiation as well as forward by using the LH/RH property. By constituting a CRLH TL MM in 2D structure, a larger aperture is obtained and consequently a small antenna with enhanced gain can be designed. By dual feeding with phase delay circuits to the 2D CRLH TL MM, a circularly polarized small antenna can be realized.
Other than artificial materials, there are some materials which can exhibit negative permeability. For example, ferrite materials show negative-mu property near magnetic resonance, although the mu changes rapidly once reaching the positive peak value, turning to quickly descend to the negative lowest value through zero, and then gradually increasing to recover positive value. Then, over the frequency range in which the permeability takes negative values, the ferrite material can be used as a negative-mu (MNG) material. However, this frequency range is rather narrow, and that often checks the practical applications.
Meanwhile, as was described previously, real MNG materials have been realized with BaFe material and permalloy composite [108]. With the BaFe material, negative mu can be obtained in a lower-frequency region, 2 to 5 GHz, while the permalloy composite exhibits negative mu in higher-frequency regions, 9 to 18 GHz and beyond. Figure 7.208 provides variation of the permeability of the permalloy composite with respect to frequency. However, since these materials have some loss and a somewhat high permittivity, this problem has been targeted to be improved.