- •Contents
- •Preface
- •Chapter 1 Introduction (K. Fujimoto)
- •Chapter 2 Small antennas (K. Fujimoto)
- •Chapter 3 Properties of small antennas (K. Fujimoto and Y. Kim)
- •Chapter 4 Fundamental limitation of small antennas (K. Fujimoto)
- •Chapter 5 Subjects related with small antennas (K. Fujimoto)
- •Chapter 6 Principles and techniques for making antennas small (H. Morishita and K. Fujimoto)
- •Chapter 7 Design and practice of small antennas I (K. Fujimoto)
- •Chapter 8 Design and practice of small antennas II (K. Fujimoto)
- •Chapter 9 Evaluation of small antenna performance (H. Morishita)
- •Chapter 10 Electromagnetic simulation (H. Morishita and Y. Kim)
- •Chapter 11 Glossary (K. Fujimoto and N. T. Hung)
- •Acknowledgements
- •1 Introduction
- •2 Small antennas
- •3 Properties of small antennas
- •3.1 Performance of small antennas
- •3.1.1 Input impedance
- •3.1.4 Gain
- •3.2 Importance of impedance matching in small antennas
- •3.3 Problems of environmental effect in small antennas
- •4 Fundamental limitations of small antennas
- •4.1 Fundamental limitations
- •4.2 Brief review of some typical work on small antennas
- •5 Subjects related with small antennas
- •5.1 Major subjects and topics
- •5.1.1 Investigation of fundamentals of small antennas
- •5.1.2 Realization of small antennas
- •5.2 Practical design problems
- •5.3 General topics
- •6 Principles and techniques for making antennas small
- •6.1 Principles for making antennas small
- •6.2 Techniques and methods for producing ESA
- •6.2.1 Lowering the antenna resonance frequency
- •6.2.1.1 SW structure
- •6.2.1.1.1 Periodic structures
- •6.2.1.1.3 Material loading on an antenna structure
- •6.2.2 Full use of volume/space circumscribing antenna
- •6.2.3 Arrangement of current distributions uniformly
- •6.2.4 Increase of radiation modes
- •6.2.4.2 Use of conjugate structure
- •6.2.4.3 Compose with different types of antennas
- •6.2.5 Applications of metamaterials to make antennas small
- •6.2.5.1 Application of SNG to small antennas
- •6.2.5.1.1 Matching in space
- •6.2.5.1.2 Matching at the load terminals
- •6.2.5.2 DNG applications
- •6.3 Techniques and methods to produce FSA
- •6.3.1 FSA composed by integration of components
- •6.3.2 FSA composed by integration of functions
- •6.3.3 FSA of composite structure
- •6.4 Techniques and methods for producing PCSA
- •6.4.2 PCSA employing a high impedance surface
- •6.5 Techniques and methods for making PSA
- •6.5.2 Simple PSA
- •6.6 Optimization techniques
- •6.6.1 Genetic algorithm
- •6.6.2 Particle swarm optimization
- •6.6.3 Topology optimization
- •6.6.4 Volumetric material optimization
- •6.6.5 Practice of optimization
- •6.6.5.1 Outline of particle swarm optimization
- •6.6.5.2 PSO application method and result
- •7 Design and practice of small antennas I
- •7.1 Design and practice
- •7.2 Design and practice of ESA
- •7.2.1 Lowering the resonance frequency
- •7.2.1.1 Use of slow wave structure
- •7.2.1.1.1 Periodic structure
- •7.2.1.1.1.1 Meander line antennas (MLA)
- •7.2.1.1.1.1.1 Dipole-type meander line antenna
- •7.2.1.1.1.1.2 Monopole-type meander line antenna
- •7.2.1.1.1.1.3 Folded-type meander line antenna
- •7.2.1.1.1.1.4 Meander line antenna mounted on a rectangular conducting box
- •7.2.1.1.1.1.5 Small meander line antennas of less than 0.1 wavelength [13]
- •7.2.1.1.1.1.6 MLAs of length L = 0.05 λ [13, 14]
- •7.2.1.1.1.2 Zigzag antennas
- •7.2.1.1.1.3 Normal mode helical antennas (NMHA)
- •7.2.1.1.1.4 Discussions on small NMHA and meander line antennas pertaining to the antenna performances
- •7.2.1.2 Extension of current path
- •7.2.2 Full use of volume/space
- •7.2.2.1.1 Meander line
- •7.2.2.1.4 Spiral antennas
- •7.2.2.1.4.1 Equiangular spiral antenna
- •7.2.2.1.4.2 Archimedean spiral antenna
- •7.2.2.1.4.3.2 Gain
- •7.2.2.1.4.4 Radiation patterns
- •7.2.2.1.4.5 Unidirectional pattern
- •7.2.2.1.4.6 Miniaturization of spiral antenna
- •7.2.2.1.4.6.1 Slot spiral antenna
- •7.2.2.1.4.6.2 Spiral antenna loaded with capacitance
- •7.2.2.1.4.6.3 Archimedean spiral antennas
- •7.2.2.1.4.6.4 Spiral antenna loaded with inductance
- •7.2.2.2 Three-dimensional (3D) structure
- •7.2.2.2.1 Koch trees
- •7.2.2.2.2 3D spiral antenna
- •7.2.2.2.3 Spherical helix
- •7.2.2.2.3.1 Folded semi-spherical monopole antennas
- •7.2.2.2.3.2 Spherical dipole antenna
- •7.2.2.2.3.3 Spherical wire antenna
- •7.2.2.2.3.4 Spherical magnetic (TE mode) dipoles
- •7.2.2.2.3.5 Hemispherical helical antenna
- •7.2.3 Uniform current distribution
- •7.2.3.1 Loading techniques
- •7.2.3.1.1 Monopole with top loading
- •7.2.3.1.2 Cross-T-wire top-loaded monopole with four open sleeves
- •7.2.3.1.3 Slot loaded with spiral
- •7.2.4 Increase of excitation mode
- •7.2.4.1.1 L-shaped quasi-self-complementary antenna
- •7.2.4.1.2 H-shaped quasi-self-complementary antenna
- •7.2.4.1.3 A half-circular disk quasi-self-complementary antenna
- •7.2.4.1.4 Sinuous spiral antenna
- •7.2.4.2 Conjugate structure
- •7.2.4.2.1 Electrically small complementary paired antenna
- •7.2.4.2.2 A combined electric-magnetic type antenna
- •7.2.4.3 Composite structure
- •7.2.4.3.1 Slot-monopole hybrid antenna
- •7.2.4.3.2 Spiral-slots loaded with inductive element
- •7.2.5 Applications of metamaterials
- •7.2.5.1 Applications of SNG (Single Negative) materials
- •7.2.5.1.1.2 Elliptical patch antenna
- •7.2.5.1.1.3 Small loop loaded with CLL
- •7.2.5.1.2 Epsilon-Negative Metamaterials (ENG MM)
- •7.2.5.2 Applications of DNG (Double Negative Materials)
- •7.2.5.2.1 Leaky wave antenna [116]
- •7.2.5.2.3 NRI (Negative Refractive Index) TL MM antennas
- •7.2.6 Active circuit applications to impedance matching
- •7.2.6.1 Antenna matching in transmitter/receiver
- •7.2.6.2 Monopole antenna
- •7.2.6.3 Loop and planar antenna
- •7.2.6.4 Microstrip antenna
- •8 Design and practice of small antennas II
- •8.1 FSA (Functionally Small Antennas)
- •8.1.1 Introduction
- •8.1.2 Integration technique
- •8.1.2.1 Enhancement/improvement of antenna performances
- •8.1.2.1.1 Bandwidth enhancement and multiband operation
- •8.1.2.1.1.1.1 E-shaped microstrip antenna
- •8.1.2.1.1.1.2 -shaped microstrip antenna
- •8.1.2.1.1.1.3 H-shaped microstrip antenna
- •8.1.2.1.1.1.4 S-shaped-slot patch antenna
- •8.1.2.1.1.2.1 Microstrip slot antennas
- •8.1.2.1.1.2.2.2 Rectangular patch with square slot
- •8.1.2.1.2.1.1 A printed λ/8 PIFA operating at penta-band
- •8.1.2.1.2.1.2 Bent-monopole penta-band antenna
- •8.1.2.1.2.1.3 Loop antenna with a U-shaped tuning element for hepta-band operation
- •8.1.2.1.2.1.4 Planar printed strip monopole for eight-band operation
- •8.1.2.1.2.2.2 Folded loop antenna
- •8.1.2.1.2.3.2 Monopole UWB antennas
- •8.1.2.1.2.3.2.1 Binomial-curved patch antenna
- •8.1.2.1.2.3.2.2 Spline-shaped antenna
- •8.1.2.1.2.3.3 UWB antennas with slot/slit embedded on the patch surface
- •8.1.2.1.2.3.3.1 A beveled square monopole patch with U-slot
- •8.1.2.1.2.3.3.2 Circular/Elliptical slot UWB antennas
- •8.1.2.1.2.3.3.3 A rectangular monopole patch with a notch and a strip
- •8.1.2.1.2.3.4.1 Pentagon-shape microstrip slot antenna
- •8.1.2.1.2.3.4.2 Sectorial loop antenna (SLA)
- •8.1.3 Integration of functions into antenna
- •8.2 Design and practice of PCSA (Physically Constrained Small Antennas)
- •8.2.2 Application of HIS (High Impedance Surface)
- •8.2.3 Applications of EBG (Electromagnetic Band Gap)
- •8.2.3.1 Miniaturization
- •8.2.3.2 Enhancement of gain
- •8.2.3.3 Enhancement of bandwidth
- •8.2.3.4 Reduction of mutual coupling
- •8.2.4 Application of DGS (Defected Ground Surface)
- •8.2.4.2 Multiband circular disk monopole patch antenna
- •8.2.5 Application of DBE (Degenerated Band Edge) structure
- •8.3 Design and practice of PSA (Physically Small Antennas)
- •8.3.1 Small antennas for radio watch/clock systems
- •8.3.2 Small antennas for RFID
- •8.3.2.1 Dipole and monopole types
- •8.3.2.3 Slot type antennas
- •8.3.2.4 Loop antenna
- •Appendix I
- •Appendix II
- •References
- •9 Evaluation of small antenna performance
- •9.1 General
- •9.2 Practical method of measurement
- •9.2.1 Measurement by using a coaxial cable
- •9.2.2 Method of measurement by using small oscillator
- •9.2.3 Method of measurement by using optical system
- •9.3 Practice of measurement
- •9.3.1 Input impedance and bandwidth
- •9.3.2 Radiation patterns and gain
- •10 Electromagnetic simulation
- •10.1 Concept of electromagnetic simulation
- •10.2 Typical electromagnetic simulators for small antennas
- •10.3 Example (balanced antennas for mobile handsets)
- •10.3.2 Antenna structure
- •10.3.3 Analytical results
- •10.3.4 Simulation for characteristics of a folded loop antenna in the vicinity of human head and hand
- •10.3.4.1 Structure of human head and hand
- •10.3.4.2 Analytical results
- •11 Glossary
- •11.1 Catalog of small antennas
- •11.2 List of small antennas
- •Index
118 |
Design and practice of small antennas I |
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0 |
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–10 |
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(dBi) |
–20 |
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Gain |
–30 |
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–40 |
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–50 |
500 |
600 |
700 |
800 |
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400 |
Frequency (MHz)
Figure 7.47 Gain characteristics of a MLA shown in Figure 7.6 ([5], copyright C 2006 IEICE).
Figure 7.49 illustrates another example; a monopole-type MLA driven by a small loop. Figure 7.50 shows the relative bandwidth with respect to the antenna size kr. Here, r is the radius of a sphere circumscribing the antenna structure and the bandwidth is shown for cases 1/Q and 2/Q. This antenna has appreciably wide bandwidth; for instance, the relative bandwidth is evaluated to be about 10%, although the size kr = 0.5.
There are many other MLAs applied practically to small equipment such as mobile phones. Discussions on these antennas will be provided in later chapters.
7.2.1.1.1.2 Zigzag antennas
A zigzag antenna composed of a line with alternating salient and re-entrant angles is depicted in Figure 7.51. The zigzag line is formed either uniformly or log-periodically. Since the zigzag line carries a slow wave (SW) with smaller phase velocity than that of free space, the antenna size can be made small. Study of zigzag antennas should go back to a paper published in 1960 [15], in which operation of typical logarithmically periodic zigzag antennas based on near-field measurement had been discussed. Later, other papers treating balanced backfire zigzag antennas [16], theory [17], input impedance [1], and analysis [18], which facilitated antenna design, were published. In [18] two types of zigzag antenna are described; one is a uniform balanced zigzag antenna over a ground plane, and another is a balanced log-periodic zigzag antenna as Figure 7.52 shows. Input impedance of a zigzag dipole antenna is depicted in Figure 7.53, where input impedance of a linear dipole antenna is shown as a comparison. Current distributions on the antenna element are calculated by solving integral equations for antennas, and the numerical results are illustrated in Figure 7.54, where (a) depicts that of the uniform zigzag antenna and (b) the log-periodic zigzag antenna. A k–β diagram is shown in Figure 7.55, where the wire diameter d of the antenna is 0.008λ and two cases in tooth angle, 20 degrees and 30 degrees, are shown.
7.2 Design and practice of ESA |
119 |
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Angle [degree] |
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Angle [degree] |
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5 |
5 |
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–5 |
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–5 |
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–15 |
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–15 |
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–25 |
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–25 |
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–35 |
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–35 |
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–45 |
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–45 |
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(a) |
(b) |
Angle [degree] |
Angle [degree] |
5 |
5 |
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–5 |
–5 |
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–15 |
–15 |
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–25 |
–25 |
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–35 |
–35 |
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–45 |
–45 |
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(c) |
(d) |
Figure 7.48 Radiation patterns of an MLA shown in Figure 7.6: (a) and (b) depict radiation patterns on the azimuth plane and the elevation plane, respectively, for antenna on the front side, and (c) and (d) show those on the azimuth plane and the elevation plane, respectively, for antenna on the back side ([5], copyright C 2006 IEICE).
120 |
Design and practice of small antennas I |
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r
Figure 7.49 A meander line monopole antenna driven by a small loop ([6], copyright C 2003
IEEE). |
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(%) |
1.5 |
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log |
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Bandwidth |
0.5 |
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2/Q |
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–1 |
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0.2 |
0.3 |
0.4 |
0.5 |
0.6 |
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0.1 |
Antenna size (kr)
Figure 7.50 Relative bandwidth of the antenna shown in Figure 7.49 ([6], copyright C 2003 IEEE).
7.2.1.1.1.3 Normal mode helical antennas (NMHA)
The NMHA (Figure 7.56) has been used practically in various small wireless terminals like mobile phones, as it can be produced in small size, and yet with higher radiation efficiency than other types of antennas having the same size. Radiation pattern is essentially the same as that of a linear dipole, and the most significant feature of the NMHA may be in the antenna structure, with which self-resonance can easily be attained, even though the size is small. Self-resonance is favorable for obtaining higher radiation efficiency, because a reactance component, which typically gives rise to a matching-network loss,
7.2 Design and practice of ESA |
121 |
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d
2
Z
Eφ
θ
Eθ
Y
ϕ
X
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2Lax |
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e1 |
e2 e3 |
e4 e5 |
e6 |
e7 |
τ |
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Figure 7.51 Zigzag antenna model with the coordinate systems ([1], copyright C 1984 IEEE).
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a |
Ground plane |
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X |
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Top view |
Rn |
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Rn+1 |
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Rn+2 |
(a) |
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Plane view of one-half |
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of the antenna |
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Figure 7.52 Two types of zigzag antenna model ([18], copyright C 1970 IEEE). |
is not necessary. It is a common understanding that the smaller the antenna becomes, the lower the antenna efficiency tends to be, but self-resonance in small antennas may resolve this problem.
Analysis of the NMHA by using a simulator is not simple, because its helical structure is constituted with very small helix radius and pitch values compared with the wavelength, and even though meshes as small as hundredths of a wavelength may be used to describe the antenna model, still accurate results are difficult to obtain. A dipole-type NMHA has been analyzed by using Method of Moments, in which unique techniques to solve the integral equations were contrived [19], and numerical data obtained by calculation are provided. Later, the design data based on the analysis described in [19] were
122 |
Design and practice of small antennas I |
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100 |
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Rin |
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Ω) |
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Zigzag |
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in |
–100 |
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Z |
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Input impedance |
–200 |
Dipole |
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Xin |
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–300 |
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Measured |
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–400 |
0.4 |
0.5 |
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0.3 |
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Axial length 2Lax (λ) |
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Figure 7.53 Impedance characteristics of a zigzag dipole antenna ([1], copyright C 1984 IEEE).
mA |
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Real part |
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Imaginary part |
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Absolute value |
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Location of bend |
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1 |
2 |
3 |
4 |
5λ |
−5
(a)Uniform zigzag antenna
(tooth angle = 60°, wire diameter = 0.008λ, distance from ground plane dv2 = 0.0625λ).
mA |
Real part of current |
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6 |
Imaginary part |
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Absolute value |
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−2 |
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−6
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1 |
2 |
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4 |
5 |
6 |
7λ |
(b)Log-periodic zigzag antenna
(α = 28°, Ψ = 32°, τ = 0.85°, wire diameter = 0.008λ).
Figure 7.54 Current distributions on (a) the uniform zigzag antenna and (b) the log-periodic zigzag antenna ([18], copyright C 1970 IEEE).
provided in a book [20], where some practical examples, including NMHAs modified to improve bandwidth and gain and so forth, were described. A further study about the analysis of NMHA has been given in [21], in which the method of analysis shown in [19] has been extended to obtain more accurate numerical results efficiently by using improved expansion function and weighting function.
7.2 Design and practice of ESA |
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0.5 |
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Calculated |
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0.4 |
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Extrapolated |
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βwire * k |
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ka |
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Tooth |
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2π |
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angle 30° |
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0.3 |
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0.2 |
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0.1 |
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Tooth angle 20° |
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0 |
0.2 |
0.4 |
0.6 |
0.8 |
1.0 |
1.2 |
1.0 |
0 |
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βo |
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a |
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2π |
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Figure 7.55 k–β diagram of a zigzag antenna ([18], copyright C 1970 IEEE). |
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l = NL
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d
l = 0
Figure 7.56 An NMHA model ([21], copyright C 2008 IEICE).
Study on NMHA has progressed as requirements for small antennas such as the NMHA have increased. Various types of NMHAs such as dielectric-loaded NMHA [21], in which efficient numerical calculation is demonstrated, log-periodic NMHA [22], folded NMHA [23], and two-wire NMHA [24], have so far been used.
Here analysis and design of the NMHA will be briefly introduced by quoting the analysis described in [19–21], and providing design data based on the analysis. The antenna model used for the analysis is shown in Figure 7.57 with the coordinate systems and antenna parameters such as helix radius a, wire diameter d, pitch of helical winding
124 |
Design and practice of small antennas I |
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x |
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#1 #2 |
#m #N |
#(2N – 1) |
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= 0 = 0 |
J( ) |
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0 |
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z 2a |
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p
y
Figure 7.57 NMHA model used for the analysis with the coordinate systems [19].
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0 |
2a
p
( 0 = √(2πa)2 + p2)
Figure 7.58 A segment consisting of two whole turns of helical structure [19].
p, helix one-turn length 0 = (2aπ )2 + p2, and number of helix windings N. The integral equation with respect to the current distribution J ( ) on the wire is
j |
2N L |
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d J ( ) |
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∂ G(, ) |
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k02 J ( )G(, ) |
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ωε0 |
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where G (, ) = |
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e−jk0r(, ) |
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Ei ( ) = − |
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Here V is the feed voltage, δ is a gap at the feed terminal, k = ω√μ0ε0 = 2π/λ stands for phase constant in free space, and r is distance between two points on , and . In order to transform the derivative of Green’s function to that of current functions and to ease solving the integral equation, the Galerkin method will be adopted along with a weighting function, which is zero at the end of the segment. The antenna model is divided into (2N – 1) segments. A segment consists of two whole turns of helical structure taken at an arbitrary place on the antenna, which has length of 2 as shown in Figure 7.58. Then, at the mth segment is described as (m – 1) L ≤ ≤ (m + 1) L, where m takes the values 1, 2, . . . , (2N − 1), and the current Jm( ) on the mth segment is expressed by Im times f ( ), which is a function having the maximum value unity at = mL, and zero
7.2 Design and practice of ESA |
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Figure 7.59 A squared cosine function ([21], copyright C 2008 IEICE).
at = (m ± 1)L. Here, Im is an unknown coefficient to be determined. Then the current on the antenna J ( ) is given by
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m=1
Im can be determined by using the circuit equation
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Now a function f ( ), a squared cosine function (Figure 7.59) is selected to give a good approximation as follows
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Through some tedious manipulations, constitutional parameters of the NMHA at resonance are analyzed [21]. In the analysis, antenna parameters of relative helix radius a/λ and relative pitch p/λ with respect to the wavelength are taken into consideration and divided into two groups A and B depending on the size. In group A, both a/λ and relative pitch p/λ are relatively larger, lying between 10−3 10−4, and in group B, they are relatively smaller with a/λ between 5 × 10−4 10−3, and p/λ between 10−4 5 × 10−4. Number of turns N at the resonance condition is expressed by illustrating the relationship between a/λ and p/λ in Figure 7.60 for the group A and in Figure 7.61 for the group B, respectively.
126 |
Design and practice of small antennas I |
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Figure 7.60 Number of turns N at resonance in relation to the helix radius a/λ and the pitch p/λ for the group A ([21], copyright C 2008 IEICE).
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Figure 7.61 Number of turns N at resonance in relation to the helix radius a/λ and the pitch p/λ for the group B ([21], copyright C 2008 IEICE).