
- •Contents
- •Preface
- •Chapter 1 Introduction (K. Fujimoto)
- •Chapter 2 Small antennas (K. Fujimoto)
- •Chapter 3 Properties of small antennas (K. Fujimoto and Y. Kim)
- •Chapter 4 Fundamental limitation of small antennas (K. Fujimoto)
- •Chapter 5 Subjects related with small antennas (K. Fujimoto)
- •Chapter 6 Principles and techniques for making antennas small (H. Morishita and K. Fujimoto)
- •Chapter 7 Design and practice of small antennas I (K. Fujimoto)
- •Chapter 8 Design and practice of small antennas II (K. Fujimoto)
- •Chapter 9 Evaluation of small antenna performance (H. Morishita)
- •Chapter 10 Electromagnetic simulation (H. Morishita and Y. Kim)
- •Chapter 11 Glossary (K. Fujimoto and N. T. Hung)
- •Acknowledgements
- •1 Introduction
- •2 Small antennas
- •3 Properties of small antennas
- •3.1 Performance of small antennas
- •3.1.1 Input impedance
- •3.1.4 Gain
- •3.2 Importance of impedance matching in small antennas
- •3.3 Problems of environmental effect in small antennas
- •4 Fundamental limitations of small antennas
- •4.1 Fundamental limitations
- •4.2 Brief review of some typical work on small antennas
- •5 Subjects related with small antennas
- •5.1 Major subjects and topics
- •5.1.1 Investigation of fundamentals of small antennas
- •5.1.2 Realization of small antennas
- •5.2 Practical design problems
- •5.3 General topics
- •6 Principles and techniques for making antennas small
- •6.1 Principles for making antennas small
- •6.2 Techniques and methods for producing ESA
- •6.2.1 Lowering the antenna resonance frequency
- •6.2.1.1 SW structure
- •6.2.1.1.1 Periodic structures
- •6.2.1.1.3 Material loading on an antenna structure
- •6.2.2 Full use of volume/space circumscribing antenna
- •6.2.3 Arrangement of current distributions uniformly
- •6.2.4 Increase of radiation modes
- •6.2.4.2 Use of conjugate structure
- •6.2.4.3 Compose with different types of antennas
- •6.2.5 Applications of metamaterials to make antennas small
- •6.2.5.1 Application of SNG to small antennas
- •6.2.5.1.1 Matching in space
- •6.2.5.1.2 Matching at the load terminals
- •6.2.5.2 DNG applications
- •6.3 Techniques and methods to produce FSA
- •6.3.1 FSA composed by integration of components
- •6.3.2 FSA composed by integration of functions
- •6.3.3 FSA of composite structure
- •6.4 Techniques and methods for producing PCSA
- •6.4.2 PCSA employing a high impedance surface
- •6.5 Techniques and methods for making PSA
- •6.5.2 Simple PSA
- •6.6 Optimization techniques
- •6.6.1 Genetic algorithm
- •6.6.2 Particle swarm optimization
- •6.6.3 Topology optimization
- •6.6.4 Volumetric material optimization
- •6.6.5 Practice of optimization
- •6.6.5.1 Outline of particle swarm optimization
- •6.6.5.2 PSO application method and result
- •7 Design and practice of small antennas I
- •7.1 Design and practice
- •7.2 Design and practice of ESA
- •7.2.1 Lowering the resonance frequency
- •7.2.1.1 Use of slow wave structure
- •7.2.1.1.1 Periodic structure
- •7.2.1.1.1.1 Meander line antennas (MLA)
- •7.2.1.1.1.1.1 Dipole-type meander line antenna
- •7.2.1.1.1.1.2 Monopole-type meander line antenna
- •7.2.1.1.1.1.3 Folded-type meander line antenna
- •7.2.1.1.1.1.4 Meander line antenna mounted on a rectangular conducting box
- •7.2.1.1.1.1.5 Small meander line antennas of less than 0.1 wavelength [13]
- •7.2.1.1.1.1.6 MLAs of length L = 0.05 λ [13, 14]
- •7.2.1.1.1.2 Zigzag antennas
- •7.2.1.1.1.3 Normal mode helical antennas (NMHA)
- •7.2.1.1.1.4 Discussions on small NMHA and meander line antennas pertaining to the antenna performances
- •7.2.1.2 Extension of current path
- •7.2.2 Full use of volume/space
- •7.2.2.1.1 Meander line
- •7.2.2.1.4 Spiral antennas
- •7.2.2.1.4.1 Equiangular spiral antenna
- •7.2.2.1.4.2 Archimedean spiral antenna
- •7.2.2.1.4.3.2 Gain
- •7.2.2.1.4.4 Radiation patterns
- •7.2.2.1.4.5 Unidirectional pattern
- •7.2.2.1.4.6 Miniaturization of spiral antenna
- •7.2.2.1.4.6.1 Slot spiral antenna
- •7.2.2.1.4.6.2 Spiral antenna loaded with capacitance
- •7.2.2.1.4.6.3 Archimedean spiral antennas
- •7.2.2.1.4.6.4 Spiral antenna loaded with inductance
- •7.2.2.2 Three-dimensional (3D) structure
- •7.2.2.2.1 Koch trees
- •7.2.2.2.2 3D spiral antenna
- •7.2.2.2.3 Spherical helix
- •7.2.2.2.3.1 Folded semi-spherical monopole antennas
- •7.2.2.2.3.2 Spherical dipole antenna
- •7.2.2.2.3.3 Spherical wire antenna
- •7.2.2.2.3.4 Spherical magnetic (TE mode) dipoles
- •7.2.2.2.3.5 Hemispherical helical antenna
- •7.2.3 Uniform current distribution
- •7.2.3.1 Loading techniques
- •7.2.3.1.1 Monopole with top loading
- •7.2.3.1.2 Cross-T-wire top-loaded monopole with four open sleeves
- •7.2.3.1.3 Slot loaded with spiral
- •7.2.4 Increase of excitation mode
- •7.2.4.1.1 L-shaped quasi-self-complementary antenna
- •7.2.4.1.2 H-shaped quasi-self-complementary antenna
- •7.2.4.1.3 A half-circular disk quasi-self-complementary antenna
- •7.2.4.1.4 Sinuous spiral antenna
- •7.2.4.2 Conjugate structure
- •7.2.4.2.1 Electrically small complementary paired antenna
- •7.2.4.2.2 A combined electric-magnetic type antenna
- •7.2.4.3 Composite structure
- •7.2.4.3.1 Slot-monopole hybrid antenna
- •7.2.4.3.2 Spiral-slots loaded with inductive element
- •7.2.5 Applications of metamaterials
- •7.2.5.1 Applications of SNG (Single Negative) materials
- •7.2.5.1.1.2 Elliptical patch antenna
- •7.2.5.1.1.3 Small loop loaded with CLL
- •7.2.5.1.2 Epsilon-Negative Metamaterials (ENG MM)
- •7.2.5.2 Applications of DNG (Double Negative Materials)
- •7.2.5.2.1 Leaky wave antenna [116]
- •7.2.5.2.3 NRI (Negative Refractive Index) TL MM antennas
- •7.2.6 Active circuit applications to impedance matching
- •7.2.6.1 Antenna matching in transmitter/receiver
- •7.2.6.2 Monopole antenna
- •7.2.6.3 Loop and planar antenna
- •7.2.6.4 Microstrip antenna
- •8 Design and practice of small antennas II
- •8.1 FSA (Functionally Small Antennas)
- •8.1.1 Introduction
- •8.1.2 Integration technique
- •8.1.2.1 Enhancement/improvement of antenna performances
- •8.1.2.1.1 Bandwidth enhancement and multiband operation
- •8.1.2.1.1.1.1 E-shaped microstrip antenna
- •8.1.2.1.1.1.2 -shaped microstrip antenna
- •8.1.2.1.1.1.3 H-shaped microstrip antenna
- •8.1.2.1.1.1.4 S-shaped-slot patch antenna
- •8.1.2.1.1.2.1 Microstrip slot antennas
- •8.1.2.1.1.2.2.2 Rectangular patch with square slot
- •8.1.2.1.2.1.1 A printed λ/8 PIFA operating at penta-band
- •8.1.2.1.2.1.2 Bent-monopole penta-band antenna
- •8.1.2.1.2.1.3 Loop antenna with a U-shaped tuning element for hepta-band operation
- •8.1.2.1.2.1.4 Planar printed strip monopole for eight-band operation
- •8.1.2.1.2.2.2 Folded loop antenna
- •8.1.2.1.2.3.2 Monopole UWB antennas
- •8.1.2.1.2.3.2.1 Binomial-curved patch antenna
- •8.1.2.1.2.3.2.2 Spline-shaped antenna
- •8.1.2.1.2.3.3 UWB antennas with slot/slit embedded on the patch surface
- •8.1.2.1.2.3.3.1 A beveled square monopole patch with U-slot
- •8.1.2.1.2.3.3.2 Circular/Elliptical slot UWB antennas
- •8.1.2.1.2.3.3.3 A rectangular monopole patch with a notch and a strip
- •8.1.2.1.2.3.4.1 Pentagon-shape microstrip slot antenna
- •8.1.2.1.2.3.4.2 Sectorial loop antenna (SLA)
- •8.1.3 Integration of functions into antenna
- •8.2 Design and practice of PCSA (Physically Constrained Small Antennas)
- •8.2.2 Application of HIS (High Impedance Surface)
- •8.2.3 Applications of EBG (Electromagnetic Band Gap)
- •8.2.3.1 Miniaturization
- •8.2.3.2 Enhancement of gain
- •8.2.3.3 Enhancement of bandwidth
- •8.2.3.4 Reduction of mutual coupling
- •8.2.4 Application of DGS (Defected Ground Surface)
- •8.2.4.2 Multiband circular disk monopole patch antenna
- •8.2.5 Application of DBE (Degenerated Band Edge) structure
- •8.3 Design and practice of PSA (Physically Small Antennas)
- •8.3.1 Small antennas for radio watch/clock systems
- •8.3.2 Small antennas for RFID
- •8.3.2.1 Dipole and monopole types
- •8.3.2.3 Slot type antennas
- •8.3.2.4 Loop antenna
- •Appendix I
- •Appendix II
- •References
- •9 Evaluation of small antenna performance
- •9.1 General
- •9.2 Practical method of measurement
- •9.2.1 Measurement by using a coaxial cable
- •9.2.2 Method of measurement by using small oscillator
- •9.2.3 Method of measurement by using optical system
- •9.3 Practice of measurement
- •9.3.1 Input impedance and bandwidth
- •9.3.2 Radiation patterns and gain
- •10 Electromagnetic simulation
- •10.1 Concept of electromagnetic simulation
- •10.2 Typical electromagnetic simulators for small antennas
- •10.3 Example (balanced antennas for mobile handsets)
- •10.3.2 Antenna structure
- •10.3.3 Analytical results
- •10.3.4 Simulation for characteristics of a folded loop antenna in the vicinity of human head and hand
- •10.3.4.1 Structure of human head and hand
- •10.3.4.2 Analytical results
- •11 Glossary
- •11.1 Catalog of small antennas
- •11.2 List of small antennas
- •Index

8.1 FSA (Functionally Small Antennas) |
327 |
|
|
Here Z11 and Z22 are self-impedance of each antenna, Zij is the mutual impedance between two antennas, and V1, V2, I1, and I2 are voltages and currents at the input port of the antenna elements as Figure 8.73(b) shows. Since the two antennas are identical and the system is symmetrical, Z11 = Z22, and Z12 = Z21. Also V1 = V2, and I1 = I2 = I. Thus the input impedance Zin of the antenna is given by
Zin = (Z11 + Z12)/2. |
(8.4) |
To obtain wide bandwidth, variation of Z11 and Z12 with respect to frequency must counteract each other. This can be achieved by optimizing the geometrical parameters of the antenna that are the loop inner and outer radii Rin and Rout and the sector angle α. When Rin and Rout, respectively, are 13 and 14 mm, relatively constant Zin is obtained for 40◦ < α < 80◦. These three parameters also determine the lowest operating frequency
f , which is given by
√
f = 2c/(π − α + 2)(Rin + Rout ) εr . (8.5)
By using this, the average radius of the loop Rav = (Rin + Rout)/2 can be determined. Then optimum α and τ = (Rin – Rout) need to be determined. Through studies of some experimentally fabricated antennas, the optimum values for these parameters are found. They are α = 60◦, Rav = 13.5 mm, and τ = 0.4 mm. This τ = 0.4 mm, which is the smallest value (thinnest loop radius), is chosen, because bandwidth becomes wider as τ tends to be smaller. With these parameters, an antenna with bandwidth of 3.7 to
11.6 GHz is obtained.
8.1.3Integration of functions into antenna
An antenna, into which active devices or circuits are integrated to enhance the antenna performance or function, is referred to as AIAS (Active Integrated Antenna System) [48]. It has received considerable attention, because the technique will provide surpassing performances or functions to antennas without enlarging the dimensions. There have been quite a few papers and books which have dealt with AIAS [49–51]. The AIAS is not necessarily ESA, but most of them are FSA. However, they have useful features in possibly being manufactured with relatively small size, compact structure, and yet low cost. Representative AIASs are those with enhanced gain [52], operating band [53, 54], and functions of reconfigurable performances such as variation of tuning frequency, switching of operating bands [55, 56], or control of radiation patterns [57–59], and so forth.
IPASs (Integrated Passive Antenna Systems) also play an important role in reducing the antenna size and enhancing the antenna performances; however, because integration of slots/slits into antenna systems has been treated in other sections, it is not mentioned here.
Here in this section, three examples will be described.
8.1.3.1An oscillator-loaded microstrip antenna
Configuration of the antenna along with the dimensions is shown in Figure 8.74 [60]. The antenna is comprised of two transmission lines, one wide line as a radiator and

328 |
Design and practice of small antennas II |
|
|
4.88
Drain
2.14
1.00
|
|
|
|
|
|
|
|
|
Transistor |
|
|
|
|
|
|
||||
|
|
|
|
|
|
|
|
|
|
|
|
||||||||
|
|
|
|
|
|
|
|
|
|
|
|
||||||||
|
|
|
|
|
|
|
|
||||||||||||
6.88 |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
4.88 |
||||
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
Capacitor |
|
|
|
|
|
|
|
|
Source |
|
|
|
|||||||
|
|
|
|
|
|
|
|
|
|||||||||||
|
|
|
|
|
|
|
|
||||||||||||
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
y 2-D
x
Gate
Figure 8.74 Geometry and dimensions of single-element antenna integrated with an oscillator along with dimensional parameters ([60], copyright C 2008 IEEE).
one narrow line to serve as a feedback loop. A transistor oscillator circuit is mounted on the wider transmission line with two source terminals connected to the central line with narrow width and the drain and gate terminals connected to the two wider lines. The length of the two radiating sections combined with the feedback loop is 3/2λg (λg: guided wavelength). Similar current and charge distributions are created by this circuit arrangement and the radiation patterns typical of a microstrip patch antenna can be obtained. The antenna pattern is etched on the microwave laminate with thickness of 0.635 mm and dielectric constant of 10.2. The transistor is an HF FET (High Frequency Field Effect Transistor) having super low-noise characteristics and gain of 8.5–9 dB over the frequency range between 6 and 12 GHz. A 1.2 pF capacitor is placed on the radiator line to serve as DC isolation between the drain and gate and at the same time provide RF feedback from the drain to gate. The transistor circuit is biased using a single 1.5 V battery between the source and drain terminals with the gate terminal remaining open.
This antenna is fabricated for testing and the performances are measured. The gain is 10 dBi at 8.5 GHz and the EIRP is 11.2 dBm. The phase noise is –87.5 dBc/Hz at 100 kHz offset, that is attributed primarily to the transmission feedback circuit in addition to low-noise characteristics of the HF FET. Figure 8.75 shows measured transmission data S21 with Vdrain = 1.2 V and Vgate = 0, and for the no-transistor case. The inset in the figure depicts radiated power.

8.1 FSA (Functionally Small Antennas) |
329 |
|
|
S21 (dB)
20 |
−20 |
|
|
|
8.56 GHz |
|
8.56 GHz |
|
|
||
|
−30 |
|
|
||
|
|
|
|
|
|
10 |
dBm−40 |
|
|
|
Vdrain = 1.2 V |
−50 |
|
|
|
||
|
|
|
|
Vgate = open |
|
|
power−60 |
|
|
|
|
|
Received |
|
|
|
No transistor |
0 |
−70 |
|
|
|
|
−80 |
|
|
|
|
|
|
|
|
|
|
|
|
−90 |
|
|
|
|
−10 |
−100 |
|
|
|
|
8.550 |
8.555 |
8.560 |
8.565 |
8.570 |
|
|
|
Frequency GHz |
|
−20
−30
−40
−50 8 8.2 8.4 8.6 8.8 9
Frequency (GHz)
Figure 8.75 Measured transmission data S21 with Vdrain and Vgate ([60], copyright C 2008 IEEE).
8.1.3.2A reconfigurable PIFA with integrated PIN-diode and varactor
By integrating a PIN-Diode for switching and a varactor for fine-tuning into a PIFA structure, an antenna capable of multiband operation for several mobile communication systems is proposed [61]. The geometry of the antenna and its dimensional parameters are illustrated in Figure 8.76, showing (a) 3D view, (b) top view, (c) side view, and
(d) front view. By varying capacitance of the varactor on an impedance-matching shortline, fine-tuning of operating frequencies can easily be achieved and by switching the radiating elements by means of the PIN-diode status (on and off), operating frequency bands largely separated can be selected. The antenna can cover four bands; USPCS (1.85–1.99 GHz), WCDMA (1.92–2.18 GHz), m-WiMAX (3.4–3.6 GHz), and WLAN (5.15–5.825 GHz).
8.1.3.3Pattern reconfigurable cubic antenna
A unique single-feed cubic antenna capable of pattern reconfigurable performance is introduced in [59]. The antenna is a metallic cubic cavity with a slot radiator on each of its six surfaces and can radiate in a 4π steradian range to receive incident waves with any polarization. The pattern reconfiguration is achieved by using a PIN diode which opens or shorts at the center of the slot on the cube, thus producing change of the radiation pattern. The operating frequency is 5 GHz. Schematic drawing of the antenna is shown in Figure 8.77. The performances of this structure are described by two aspects; resonance modes of the cube which radiate through the slot and the resonance of the slot. The cube dimension a can be determined by taking these two effects into account and
considering the first fundamental modes TE011, TE101, and TE110. With cube dimension a = 37.5 mm, slot length ls = 27 mm, and probe length lp = 27 mm, the resonance
frequencies of the cube and the slot are 5.8 GHz (bandwidth is about 2.5%) and 5 GHz

330 |
Design and practice of small antennas II |
|
|
(x0,y0)
(b)
(0,0)
PIN diode
Z
X |
Y |
Varactor |
|
|
(c) |
||
(d) |
|
||
Folded part |
Short line |
||
|
|||
(a) |
Ground |
Feeding |
|
|
|||
|
|
conductor |
|
|
W |
L |
|
|
|
|
|
G2 |
|
|
L1 |
|
Substrate, εr = 4.4 |
|
|
|
W |
|
|
6 |
|
L7 |
|
|
Folded |
Varactor |
(c) |
part |
|
|
|
Short |
|
|
line |
|
Ground |
|
|
SMA connnector |
|
|
PIN diode |
Feeder |
|
||
|
|
W2 |
W1 |
|||
(x y |
) |
|
|
|
||
0, 0 |
|
|
|
|
|
|
|
|
|
|
L |
3 |
G2 |
|
L5 |
Additional |
|
L4 |
Short |
|
|
|
radiator |
|
line |
||
|
|
|
|
|
||
|
|
|
|
|
|
L2 |
(b) |
|
W4 |
G4 |
W3 |
G3 |
|
|
|
|
|
L1 |
||
L |
|
Main radiator |
|
|
|
|
6 |
|
|
|
|
||
|
|
W5 |
|
|
|
|
|
|
W7 |
|
|
|
G1 |
|
|
|
|
|
|
H1 |
|
|
|
|
|
|
L3 |
|
|
Feeding conductor |
|
|
0.6 φ |
(d) |
H |
Varactor |
|
||
|
|
Short |
|
|
line |
|
|
SMA connnector |
Figure 8.76 Geometry of a PIFA loaded with a PIN-diode: (a) 3D view, (b) top view, (c) side view, and (d) front view ([61], copyright C 2010 IEEE).
Figure 8.77 3D view of a cubic reconfigurable antenna ([59], copyright C 2009 IEEE).
(bandwidth is about 6.5%), respectively. To have two frequencies close in order to obtain a wider bandwidth, the cube length and probe length are changed to ls = 39 mm and lp = 38 mm, respectively and achieved the bandwidth of 11.3% at 5.2 GHz with the resonance frequencies of the cube at 5.05 GHz and the slot at 5.4 GHz, respectively. The

8.1 FSA (Functionally Small Antennas) |
331 |
|
|
Gϕ |
Gθ |
z |
z |
Theta |
Theta |
|
(a) |
y |
y |
Phi |
Phi |
|
|
z |
z |
Theta |
Theta |
|
(b) |
y |
y |
Phi |
Phi |
z |
z |
Theta |
Theta |
|
|
|
(c) |
y |
y |
Phi |
Phi |
Figure 8.78 Simulated radiation patterns along ϕ (on left) and θ (on right) for (a) configuration 1,
(b) configuration 2, and (c) configuration 3 ([59], copyright C 2009 IEEE).
radiation patterns are varied by short-circuiting or open-circuiting the center of the slot, resulting in cancelling or producing radiation. This action can be performed by using a PIN diode which switches the state of on or off to cause shortor open-circuiting the slot. Reconfiguration of the pattern is realized by selecting which slots are short-circuited. Three configurations 1, 2, and 3 are considered; each one contains two short-circuited slots on the lower sides and one on the upper side on the cube. Figure 8.78(a), (b), and (c), respectively, illustrate the simulated radiation patterns at 5.4 GHz for the configurations 1, 2, and 3, for Gϕ (gain pattern along ϕ) on the left and Gθ (gain pattern along θ ) on the right. Switching the configuration is equivalent to rotating the cube around the probe on an angle of 120◦. As can be noted in Figure 8.78 the antenna radiates in a 4π steradian range with a maximum gain toward a certain direction, and hence by switching the configuration the maximum gain direction changes. The maximum gain is evaluated as approximately 3.7 dBi. In addition to the variation in the maximum gain direction, the radiated powers, in other words Gϕ and Gθ , in a given direction are not identical