
- •Contents
- •Preface
- •Chapter 1 Introduction (K. Fujimoto)
- •Chapter 2 Small antennas (K. Fujimoto)
- •Chapter 3 Properties of small antennas (K. Fujimoto and Y. Kim)
- •Chapter 4 Fundamental limitation of small antennas (K. Fujimoto)
- •Chapter 5 Subjects related with small antennas (K. Fujimoto)
- •Chapter 6 Principles and techniques for making antennas small (H. Morishita and K. Fujimoto)
- •Chapter 7 Design and practice of small antennas I (K. Fujimoto)
- •Chapter 8 Design and practice of small antennas II (K. Fujimoto)
- •Chapter 9 Evaluation of small antenna performance (H. Morishita)
- •Chapter 10 Electromagnetic simulation (H. Morishita and Y. Kim)
- •Chapter 11 Glossary (K. Fujimoto and N. T. Hung)
- •Acknowledgements
- •1 Introduction
- •2 Small antennas
- •3 Properties of small antennas
- •3.1 Performance of small antennas
- •3.1.1 Input impedance
- •3.1.4 Gain
- •3.2 Importance of impedance matching in small antennas
- •3.3 Problems of environmental effect in small antennas
- •4 Fundamental limitations of small antennas
- •4.1 Fundamental limitations
- •4.2 Brief review of some typical work on small antennas
- •5 Subjects related with small antennas
- •5.1 Major subjects and topics
- •5.1.1 Investigation of fundamentals of small antennas
- •5.1.2 Realization of small antennas
- •5.2 Practical design problems
- •5.3 General topics
- •6 Principles and techniques for making antennas small
- •6.1 Principles for making antennas small
- •6.2 Techniques and methods for producing ESA
- •6.2.1 Lowering the antenna resonance frequency
- •6.2.1.1 SW structure
- •6.2.1.1.1 Periodic structures
- •6.2.1.1.3 Material loading on an antenna structure
- •6.2.2 Full use of volume/space circumscribing antenna
- •6.2.3 Arrangement of current distributions uniformly
- •6.2.4 Increase of radiation modes
- •6.2.4.2 Use of conjugate structure
- •6.2.4.3 Compose with different types of antennas
- •6.2.5 Applications of metamaterials to make antennas small
- •6.2.5.1 Application of SNG to small antennas
- •6.2.5.1.1 Matching in space
- •6.2.5.1.2 Matching at the load terminals
- •6.2.5.2 DNG applications
- •6.3 Techniques and methods to produce FSA
- •6.3.1 FSA composed by integration of components
- •6.3.2 FSA composed by integration of functions
- •6.3.3 FSA of composite structure
- •6.4 Techniques and methods for producing PCSA
- •6.4.2 PCSA employing a high impedance surface
- •6.5 Techniques and methods for making PSA
- •6.5.2 Simple PSA
- •6.6 Optimization techniques
- •6.6.1 Genetic algorithm
- •6.6.2 Particle swarm optimization
- •6.6.3 Topology optimization
- •6.6.4 Volumetric material optimization
- •6.6.5 Practice of optimization
- •6.6.5.1 Outline of particle swarm optimization
- •6.6.5.2 PSO application method and result
- •7 Design and practice of small antennas I
- •7.1 Design and practice
- •7.2 Design and practice of ESA
- •7.2.1 Lowering the resonance frequency
- •7.2.1.1 Use of slow wave structure
- •7.2.1.1.1 Periodic structure
- •7.2.1.1.1.1 Meander line antennas (MLA)
- •7.2.1.1.1.1.1 Dipole-type meander line antenna
- •7.2.1.1.1.1.2 Monopole-type meander line antenna
- •7.2.1.1.1.1.3 Folded-type meander line antenna
- •7.2.1.1.1.1.4 Meander line antenna mounted on a rectangular conducting box
- •7.2.1.1.1.1.5 Small meander line antennas of less than 0.1 wavelength [13]
- •7.2.1.1.1.1.6 MLAs of length L = 0.05 λ [13, 14]
- •7.2.1.1.1.2 Zigzag antennas
- •7.2.1.1.1.3 Normal mode helical antennas (NMHA)
- •7.2.1.1.1.4 Discussions on small NMHA and meander line antennas pertaining to the antenna performances
- •7.2.1.2 Extension of current path
- •7.2.2 Full use of volume/space
- •7.2.2.1.1 Meander line
- •7.2.2.1.4 Spiral antennas
- •7.2.2.1.4.1 Equiangular spiral antenna
- •7.2.2.1.4.2 Archimedean spiral antenna
- •7.2.2.1.4.3.2 Gain
- •7.2.2.1.4.4 Radiation patterns
- •7.2.2.1.4.5 Unidirectional pattern
- •7.2.2.1.4.6 Miniaturization of spiral antenna
- •7.2.2.1.4.6.1 Slot spiral antenna
- •7.2.2.1.4.6.2 Spiral antenna loaded with capacitance
- •7.2.2.1.4.6.3 Archimedean spiral antennas
- •7.2.2.1.4.6.4 Spiral antenna loaded with inductance
- •7.2.2.2 Three-dimensional (3D) structure
- •7.2.2.2.1 Koch trees
- •7.2.2.2.2 3D spiral antenna
- •7.2.2.2.3 Spherical helix
- •7.2.2.2.3.1 Folded semi-spherical monopole antennas
- •7.2.2.2.3.2 Spherical dipole antenna
- •7.2.2.2.3.3 Spherical wire antenna
- •7.2.2.2.3.4 Spherical magnetic (TE mode) dipoles
- •7.2.2.2.3.5 Hemispherical helical antenna
- •7.2.3 Uniform current distribution
- •7.2.3.1 Loading techniques
- •7.2.3.1.1 Monopole with top loading
- •7.2.3.1.2 Cross-T-wire top-loaded monopole with four open sleeves
- •7.2.3.1.3 Slot loaded with spiral
- •7.2.4 Increase of excitation mode
- •7.2.4.1.1 L-shaped quasi-self-complementary antenna
- •7.2.4.1.2 H-shaped quasi-self-complementary antenna
- •7.2.4.1.3 A half-circular disk quasi-self-complementary antenna
- •7.2.4.1.4 Sinuous spiral antenna
- •7.2.4.2 Conjugate structure
- •7.2.4.2.1 Electrically small complementary paired antenna
- •7.2.4.2.2 A combined electric-magnetic type antenna
- •7.2.4.3 Composite structure
- •7.2.4.3.1 Slot-monopole hybrid antenna
- •7.2.4.3.2 Spiral-slots loaded with inductive element
- •7.2.5 Applications of metamaterials
- •7.2.5.1 Applications of SNG (Single Negative) materials
- •7.2.5.1.1.2 Elliptical patch antenna
- •7.2.5.1.1.3 Small loop loaded with CLL
- •7.2.5.1.2 Epsilon-Negative Metamaterials (ENG MM)
- •7.2.5.2 Applications of DNG (Double Negative Materials)
- •7.2.5.2.1 Leaky wave antenna [116]
- •7.2.5.2.3 NRI (Negative Refractive Index) TL MM antennas
- •7.2.6 Active circuit applications to impedance matching
- •7.2.6.1 Antenna matching in transmitter/receiver
- •7.2.6.2 Monopole antenna
- •7.2.6.3 Loop and planar antenna
- •7.2.6.4 Microstrip antenna
- •8 Design and practice of small antennas II
- •8.1 FSA (Functionally Small Antennas)
- •8.1.1 Introduction
- •8.1.2 Integration technique
- •8.1.2.1 Enhancement/improvement of antenna performances
- •8.1.2.1.1 Bandwidth enhancement and multiband operation
- •8.1.2.1.1.1.1 E-shaped microstrip antenna
- •8.1.2.1.1.1.2 -shaped microstrip antenna
- •8.1.2.1.1.1.3 H-shaped microstrip antenna
- •8.1.2.1.1.1.4 S-shaped-slot patch antenna
- •8.1.2.1.1.2.1 Microstrip slot antennas
- •8.1.2.1.1.2.2.2 Rectangular patch with square slot
- •8.1.2.1.2.1.1 A printed λ/8 PIFA operating at penta-band
- •8.1.2.1.2.1.2 Bent-monopole penta-band antenna
- •8.1.2.1.2.1.3 Loop antenna with a U-shaped tuning element for hepta-band operation
- •8.1.2.1.2.1.4 Planar printed strip monopole for eight-band operation
- •8.1.2.1.2.2.2 Folded loop antenna
- •8.1.2.1.2.3.2 Monopole UWB antennas
- •8.1.2.1.2.3.2.1 Binomial-curved patch antenna
- •8.1.2.1.2.3.2.2 Spline-shaped antenna
- •8.1.2.1.2.3.3 UWB antennas with slot/slit embedded on the patch surface
- •8.1.2.1.2.3.3.1 A beveled square monopole patch with U-slot
- •8.1.2.1.2.3.3.2 Circular/Elliptical slot UWB antennas
- •8.1.2.1.2.3.3.3 A rectangular monopole patch with a notch and a strip
- •8.1.2.1.2.3.4.1 Pentagon-shape microstrip slot antenna
- •8.1.2.1.2.3.4.2 Sectorial loop antenna (SLA)
- •8.1.3 Integration of functions into antenna
- •8.2 Design and practice of PCSA (Physically Constrained Small Antennas)
- •8.2.2 Application of HIS (High Impedance Surface)
- •8.2.3 Applications of EBG (Electromagnetic Band Gap)
- •8.2.3.1 Miniaturization
- •8.2.3.2 Enhancement of gain
- •8.2.3.3 Enhancement of bandwidth
- •8.2.3.4 Reduction of mutual coupling
- •8.2.4 Application of DGS (Defected Ground Surface)
- •8.2.4.2 Multiband circular disk monopole patch antenna
- •8.2.5 Application of DBE (Degenerated Band Edge) structure
- •8.3 Design and practice of PSA (Physically Small Antennas)
- •8.3.1 Small antennas for radio watch/clock systems
- •8.3.2 Small antennas for RFID
- •8.3.2.1 Dipole and monopole types
- •8.3.2.3 Slot type antennas
- •8.3.2.4 Loop antenna
- •Appendix I
- •Appendix II
- •References
- •9 Evaluation of small antenna performance
- •9.1 General
- •9.2 Practical method of measurement
- •9.2.1 Measurement by using a coaxial cable
- •9.2.2 Method of measurement by using small oscillator
- •9.2.3 Method of measurement by using optical system
- •9.3 Practice of measurement
- •9.3.1 Input impedance and bandwidth
- •9.3.2 Radiation patterns and gain
- •10 Electromagnetic simulation
- •10.1 Concept of electromagnetic simulation
- •10.2 Typical electromagnetic simulators for small antennas
- •10.3 Example (balanced antennas for mobile handsets)
- •10.3.2 Antenna structure
- •10.3.3 Analytical results
- •10.3.4 Simulation for characteristics of a folded loop antenna in the vicinity of human head and hand
- •10.3.4.1 Structure of human head and hand
- •10.3.4.2 Analytical results
- •11 Glossary
- •11.1 Catalog of small antennas
- •11.2 List of small antennas
- •Index

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Principles and techniques for making antennas small |
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Feed Ground
Figure 6.17 Extended current paths with a notch and a slot producing multiband operation.
Figure 6.18 Array of thin wires to compose negative permittivity surface [15, 16].
6.2.1.1.3 Material loading on an antenna structure
Loading of materials such as dielectric, magnetic, or metamaterials on an antenna structure is a simple way to produce the SW structure. Since the phase velocity vp in such materials is expressed by using the permittivity ε of the dielectric material and the permeability μ of the magnetic material, as
vp = ω0/β = 1/(εμ)1/2. |
(6.6) |
From this, vp is shown to be smaller than c, because |
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vp/c = (ε0μ0)1/2/(εμ)1/2 = 1/(εr μr )1/2 < 1 |
(6.7) |
since ε = εrε0 and μ = μrμ0, and εr and μr are usually greater than unity.
Making use of metamaterials is another useful way to produce SW structure. The metamaterials are known as materials that exhibit uncommon electromagnetic properties not available in nature [15–17]. In reality, metamaterials do not exist; however, equivalent materials have been realized first by using a dense array of thin wires (Figure 6.18), and an array of split ring resonators (SRR) (Figure 6.19) [18–20]. The former exhibits a property of negative permittivity ε and the latter shows negative permeability μ and

6.2 Techniques and methods for producing ESA |
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Figure 6.19 Array of sprit ring resonators (SRR) to compose negative permeability surface [15, 16].
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Figure 6.20 A T-circuit model representing transmission line (one segment of the periodic connection) [26].
applications of them to antennas have been described in many papers [16–17, 21–23]. Among them, Itoh demonstrated an artificial metamaterial using transmission lines, which achieved equivalent metamaterial performances that exhibit a left-handed (LH) property that resulted from negative permeability and negative permittivity at the same time [24, 25].
Plane-wave propagation in isotropic and homogeneous dielectric can be treated by the concept of TEM propagation in a transmission line, which is comprised of periodic connections of a T-shaped circuit consisting of a series per-unit-length impedance Zs, and a shunt per-unit-length admittance Yp as shown in Figure 6.20 [26]. Here, characteristic impedance Z = Zs /Yp and propagation constant γ = Zs Yp, and Zs and Yp, respectively, are described as
Zs (ω) = jωμ
(6.8)
Yp(ω) = jωε

54 |
Principles and techniques for making antennas small |
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L / 2 L / 2 |
2C |
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Figure 6.21 The equivalent transmission line model consisting of circuit parameters L-C; (a) L in series and C in shunt and (b) L-C interchanged circuit [26].
where ε and μ, respectively are the dielectric permittivity and the magnetic permeability of the propagation medium [27]. The transmission line model consisting of circuit parameters C and L, is illustrated in Figure 6.21(a). From Eq. (6.8), the effective constitutive parameters εeff and μeff, respectively, are described as
εeff = C/ l
(6.9)
μeff = L/ l
where l is the unit length.
Interchange of C and L, results in the dual transmission line as shown in Figure 6.21(b). By using (6.8), εeff and μeff can be related with the circuit parameters as
εeff = −1/(ω2 Ll)
(6.10)
μeff = −1/(ω2Cl)
The dispersion characteristics of the equivalent circuit are the same as that shown previously in Figure 6.5(a) and (b). In the SW (Slow Wave) structure, a wave propagates with the phase constant β greater than that in free space k. The transmission line with the constitutive parameters –ε and –μ that are given by (6.10) is considered as the LH (Left Handed) media where the phase velocity vp and the group velocity vg are anti-parallel, and the wave propagates backward [28]. The LH media is characterized by the property of negative propagation constant –k, the attribute of –ε and –μ. The name is originated from the term Right-Hand (RH) Rule that is derived from use of a right hand to indicate the direction of the wave vector k; for example, E × H = S, by the thumb of the right hand as Figure 6.22 shows. In the LH media, the direction of the wave vector k is the opposite to that of the cross product vector S, while in the RH case, directions of both k and S are the same as Figure 6.22(b) illustrates.
In reality, however, this transmission line cannot be implemented perfectly, because there exists unavoidable parasitic series inductance Lp and shunt capacitance Cp. Then a CRLH (Composite Right/Left-Handed) model shown in Figure 6.23 is considered as the most general form of a structure with the LH attributes [26]. The dispersion characteristics of the CRLH transmission line model is depicted in Figure 6.24, which shows a case for ω2 > ω1 [26]. The region between two frequencies ω1 and ω2 denotes a bandgap, where waves do not propagate. This bandgap is generally called the EBG (Electromagnetic Band Gap).

6.2 Techniques and methods for producing ESA |
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Figure 6.22 The Right-handed Rule; (a) demonstration for vector cross product and (b) the Right-handed (RH) and Left-handed (LH) cases.
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LL CR
Figure 6.23 CRLH model (one segment of equivalent transmission line) [26].
Figure 6.24 Dispersion characteristics of the CRLH transmission line model [26].
The effective constitutive parameters εeff and μeff of this CRLH model are given by
εeff = (CR − 1/ω2 L L )/ l . |
(6.11) |
μeff = (L R − 1/ω2CL )/ l |
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This indicates the nature of CRLH of the artificial transmission line. An SNG transmission line can be realized by loading a host line with series capacitors (corresponding to
–μ lines) or shunt inductors (corresponding to –ε lines).