
- •Contents
- •Preface
- •1 Spread spectrum signals and systems
- •1.1 Basic definition
- •1.2 Historical sketch
- •2 Classical reception problems and signal design
- •2.1 Gaussian channel, general reception problem and optimal decision rules
- •2.2 Binary data transmission (deterministic signals)
- •2.3 M-ary data transmission: deterministic signals
- •2.4 Complex envelope of a bandpass signal
- •2.5 M-ary data transmission: noncoherent signals
- •2.6 Trade-off between orthogonal-coding gain and bandwidth
- •2.7 Examples of orthogonal signal sets
- •2.7.1 Time-shift coding
- •2.7.2 Frequency-shift coding
- •2.7.3 Spread spectrum orthogonal coding
- •2.8 Signal parameter estimation
- •2.8.1 Problem statement and estimation rule
- •2.8.2 Estimation accuracy
- •2.9 Amplitude estimation
- •2.10 Phase estimation
- •2.11 Autocorrelation function and matched filter response
- •2.12 Estimation of the bandpass signal time delay
- •2.12.1 Estimation algorithm
- •2.12.2 Estimation accuracy
- •2.13 Estimation of carrier frequency
- •2.14 Simultaneous estimation of time delay and frequency
- •2.15 Signal resolution
- •2.16 Summary
- •Problems
- •Matlab-based problems
- •3 Merits of spread spectrum
- •3.1 Jamming immunity
- •3.1.1 Narrowband jammer
- •3.1.2 Barrage jammer
- •3.2 Low probability of detection
- •3.3 Signal structure secrecy
- •3.4 Electromagnetic compatibility
- •3.5 Propagation effects in wireless systems
- •3.5.1 Free-space propagation
- •3.5.2 Shadowing
- •3.5.3 Multipath fading
- •3.5.4 Performance analysis
- •3.6 Diversity
- •3.6.1 Combining modes
- •3.6.2 Arranging diversity branches
- •3.7 Multipath diversity and RAKE receiver
- •Problems
- •Matlab-based problems
- •4 Multiuser environment: code division multiple access
- •4.1 Multiuser systems and the multiple access problem
- •4.2 Frequency division multiple access
- •4.3 Time division multiple access
- •4.4 Synchronous code division multiple access
- •4.5 Asynchronous CDMA
- •4.6 Asynchronous CDMA in the cellular networks
- •4.6.1 The resource reuse problem and cellular systems
- •4.6.2 Number of users per cell in asynchronous CDMA
- •Problems
- •Matlab-based problems
- •5 Discrete spread spectrum signals
- •5.1 Spread spectrum modulation
- •5.2 General model and categorization of discrete signals
- •5.3 Correlation functions of APSK signals
- •5.4 Calculating correlation functions of code sequences
- •5.5 Correlation functions of FSK signals
- •5.6 Processing gain of discrete signals
- •Problems
- •Matlab-based problems
- •6 Spread spectrum signals for time measurement, synchronization and time-resolution
- •6.1 Demands on ACF: revisited
- •6.2 Signals with continuous frequency modulation
- •6.3 Criterion of good aperiodic ACF of APSK signals
- •6.4 Optimization of aperiodic PSK signals
- •6.5 Perfect periodic ACF: minimax binary sequences
- •6.6 Initial knowledge on finite fields and linear sequences
- •6.6.1 Definition of a finite field
- •6.6.2 Linear sequences over finite fields
- •6.6.3 m-sequences
- •6.7 Periodic ACF of m-sequences
- •6.8 More about finite fields
- •6.9 Legendre sequences
- •6.10 Binary codes with good aperiodic ACF: revisited
- •6.11 Sequences with perfect periodic ACF
- •6.11.1 Binary non-antipodal sequences
- •6.11.2 Polyphase codes
- •6.11.3 Ternary sequences
- •6.12 Suppression of sidelobes along the delay axis
- •6.12.1 Sidelobe suppression filter
- •6.12.2 SNR loss calculation
- •6.13 FSK signals with optimal aperiodic ACF
- •Problems
- •Matlab-based problems
- •7 Spread spectrum signature ensembles for CDMA applications
- •7.1 Data transmission via spread spectrum
- •7.1.1 Direct sequence spreading: BPSK data modulation and binary signatures
- •7.1.2 DS spreading: general case
- •7.1.3 Frequency hopping spreading
- •7.2 Designing signature ensembles for synchronous DS CDMA
- •7.2.1 Problem formulation
- •7.2.2 Optimizing signature sets in minimum distance
- •7.2.3 Welch-bound sequences
- •7.3 Approaches to designing signature ensembles for asynchronous DS CDMA
- •7.4 Time-offset signatures for asynchronous CDMA
- •7.5 Examples of minimax signature ensembles
- •7.5.1 Frequency-offset binary m-sequences
- •7.5.2 Gold sets
- •7.5.3 Kasami sets and their extensions
- •7.5.4 Kamaletdinov ensembles
- •Problems
- •Matlab-based problems
- •8 DS spread spectrum signal acquisition and tracking
- •8.1 Acquisition and tracking procedures
- •8.2 Serial search
- •8.2.1 Algorithm model
- •8.2.2 Probability of correct acquisition and average number of steps
- •8.2.3 Minimizing average acquisition time
- •8.3 Acquisition acceleration techniques
- •8.3.1 Problem statement
- •8.3.2 Sequential cell examining
- •8.3.3 Serial-parallel search
- •8.3.4 Rapid acquisition sequences
- •8.4 Code tracking
- •8.4.1 Delay estimation by tracking
- •8.4.2 Early–late DLL discriminators
- •8.4.3 DLL noise performance
- •Problems
- •Matlab-based problems
- •9 Channel coding in spread spectrum systems
- •9.1 Preliminary notes and terminology
- •9.2 Error-detecting block codes
- •9.2.1 Binary block codes and detection capability
- •9.2.2 Linear codes and their polynomial representation
- •9.2.3 Syndrome calculation and error detection
- •9.2.4 Choice of generator polynomials for CRC
- •9.3 Convolutional codes
- •9.3.1 Convolutional encoder
- •9.3.2 Trellis diagram, free distance and asymptotic coding gain
- •9.3.3 The Viterbi decoding algorithm
- •9.3.4 Applications
- •9.4 Turbo codes
- •9.4.1 Turbo encoders
- •9.4.2 Iterative decoding
- •9.4.3 Performance
- •9.4.4 Applications
- •9.5 Channel interleaving
- •Problems
- •Matlab-based problems
- •10 Some advancements in spread spectrum systems development
- •10.1 Multiuser reception and suppressing MAI
- •10.1.1 Optimal (ML) multiuser rule for synchronous CDMA
- •10.1.2 Decorrelating algorithm
- •10.1.3 Minimum mean-square error detection
- •10.1.4 Blind MMSE detector
- •10.1.5 Interference cancellation
- •10.1.6 Asynchronous multiuser detectors
- •10.2 Multicarrier modulation and OFDM
- •10.2.1 Multicarrier DS CDMA
- •10.2.2 Conventional MC transmission and OFDM
- •10.2.3 Multicarrier CDMA
- •10.2.4 Applications
- •10.3 Transmit diversity and space–time coding in CDMA systems
- •10.3.1 Transmit diversity and the space–time coding problem
- •10.3.2 Efficiency of transmit diversity
- •10.3.3 Time-switched space–time code
- •10.3.4 Alamouti space–time code
- •10.3.5 Transmit diversity in spread spectrum applications
- •Problems
- •Matlab-based problems
- •11 Examples of operational wireless spread spectrum systems
- •11.1 Preliminary remarks
- •11.2 Global positioning system
- •11.2.1 General system principles and architecture
- •11.2.2 GPS ranging signals
- •11.2.3 Signal processing
- •11.2.4 Accuracy
- •11.2.5 GLONASS and GNSS
- •11.2.6 Applications
- •11.3 Air interfaces cdmaOne (IS-95) and cdma2000
- •11.3.1 Introductory remarks
- •11.3.2 Spreading codes of IS-95
- •11.3.3 Forward link channels of IS-95
- •11.3.3.1 Pilot channel
- •11.3.3.2 Synchronization channel
- •11.3.3.3 Paging channels
- •11.3.3.4 Traffic channels
- •11.3.3.5 Forward link modulation
- •11.3.3.6 MS processing of forward link signal
- •11.3.4 Reverse link of IS-95
- •11.3.4.1 Reverse link traffic channel
- •11.3.4.2 Access channel
- •11.3.4.3 Reverse link modulation
- •11.3.5 Evolution of air interface cdmaOne to cdma2000
- •11.4 Air interface UMTS
- •11.4.1 Preliminaries
- •11.4.2 Types of UMTS channels
- •11.4.3 Dedicated physical uplink channels
- •11.4.4 Common physical uplink channels
- •11.4.5 Uplink channelization codes
- •11.4.6 Uplink scrambling
- •11.4.7 Mapping downlink transport channels to physical channels
- •11.4.8 Downlink physical channels format
- •11.4.9 Downlink channelization codes
- •11.4.10 Downlink scrambling codes
- •11.4.11 Synchronization channel
- •11.4.11.1 General structure
- •11.4.11.2 Primary synchronization code
- •11.4.11.3 Secondary synchronization code
- •References
- •Index

Signal acquisition and tracking |
253 |
Fu
F
δF
τ |
δτ |
τu |
|
Figure 8.1 Search zone and signal position on the delay–frequency plane
should find out which one of M cells contains the signal, i.e. test M competitive hypotheses (see Section 2.8). If the optimal testing procedure were used, M correlations (2.74) would be computed in parallel for values and F corresponding to cell centres, and then the decision made in favour of , F corresponding to the highest correlation. Typical acquisition procedures, however, utilize the long presence of signal at the receiver input, which permits calculation of only several (not all M) correlations at a time. If none of them is large enough, the decision is taken that there is no true cell (i.e. containing the signal) among those tested and the search continues by examining another group of cells. The procedure goes on this way until some correlation is recognized as large enough to suggest that the corresponding cell is true. This terminates the acquisition, after which a tracking loop starts working, targetted by the estimations obtained. Remarkable research has been done concerning acquisition algorithms and strategies (see, for example, the bibliography in [77]). Below we will limit ourselves to only very brief discussion, starting with the simplest version of acquisition.
8.2 Serial search
8.2.1 Algorithm model
In a serial search only one cell at a time is tested, i.e. only a single correlation is calculated of the observation and a local signal replica, having some specific time– frequency shift. The correlation magnitude is then analysed in order to decide whether the cell is true or false. Various criteria may serve to take the decision. For example, the search may continue until all the cells inside the uncertainty region (see Figure 8.1) are tested, all the time storing in memory the maximal correlation observed up to now along with the values of , F corresponding to it. Then, after the last cell is analysed, the cell believed to be true is known automatically by its coordinates kept in memory, and all to be done is just reading them out. This strategy is equivalent to implementing the ML estimation rule, but calculating the necessary correlations not simultaneously but sequentially in time for successively arriving signal segments.
Still more typical of practical receivers is another version of a serial search, where the currently found correlation magnitude is just compared with a threshold [6,9,77]. If the

254 |
|
|
|
|
|
|
|
|
|
Spread Spectrum and CDMA |
||
|
|
|
|
|
|
|
|
|
|
|
||
|
|
|
|
|
|
|
|
|
|
Phase found |
||
|
y(t) |
|
|
|
|
|
|
|
|
|
|
|
|
Correlator |
|
|
Control |
|
|
|
Code |
|
|
||
|
|
|
|
|
logic |
|
|
|
generator |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
||
|
|
|
|
|
|
|
|
|
|
|
|
|
s(t – τ)
Threshold
Figure 8.2 Serial search of a spreading code phase
correlation is larger than the threshold the decision is made that the current cell is true and the search finishes. Otherwise the search system examines the next cell and so forth.
From the point of view of performance analysis it does not matter how many parameters are unknown and to be estimated in the course of searching: both time and frequency (or whatever else) or some one of them. The only material thing is the overall number of cells to be checked. Yet to make further deliberations more transparent we will treat them as though an acquisition consists in only measuring the time delay of a received signal, the frequency being known a priori with sufficient precision. Figure 8.2 presents the structure running a serial search in this case. When a spreading code is periodic, the maximal uncertainty time zone may span only one period and all greater delays are reduced to fall within one period. In this light the name ‘phase’ is also appropriate as a synonym of delay of a periodic code [2,6,9] and transferring from one cell to the next in the uncertainty region means just changing the phase of the local code replica. When a current correlation is below the threshold the search control logic orders the local generator to increment the phase of the code replica s(t ) at its output by one chip or a split chip, and the procedure goes over to examining the next cell. If the current correlation exceeds the threshold the control logic signals that acquisition is finished and the code generator keeps the code phase corresponding to the cell declared to be true. In the following sections we discuss the performance of this algorithm based on the analysis of [78] and referring the reader inclined to learn more to [6,9,77,79–81].
8.2.2 Probability of correct acquisition and average number of steps
To simplify the analysis (still with no compromise of the basic regularities), let us assume that the local code replica is shifted versus the received signal by an integer number of chip durations. Then with L being the code period there are L possible code phases altogether, only one of which is true. To put it differently, there may be at most L search cells and every transition from one cell to the next means incrementing the code phase by one chip duration. Very often checking all of these L cells in the course of a search is needless thanks to reliable prior information shortening the search region to only M of L cells. Let us begin with an assumption that the search starts with the least favourable empty cell inside the uncertainty region, i.e. most distant from the true one. Figure 8.3 illustrates this premise: the first reaching of the true cell (black circle) takes place only after passing safely over M 1 empty cells (white circles).

Signal acquisition and tracking |
|
|
|
|
|
|
|
255 |
||
1 |
2 |
3 |
M – 1 |
M |
|
1 |
M – 1 |
M |
|
1 |
1 – pf |
1 – pf |
|
1 – pf |
|
1 – pd |
|
1 – pf |
|
1 – pd |
|
pf |
pf |
pf |
pf |
|
pd |
pf |
pf |
|
pd |
pf |
End
Figure 8.3 A serial search of a code within the uncertainty region of M cells
In order to achieve a reliable distinction between correlation levels in the false and true cells the search system should calculate the correlation in every cell over a sufficient time interval: dwell time. Whatever dwell time and threshold are set up, decisions on whether a cell is true or false cannot be absolutely faultless. One sort of possible error is a false alarm (see Section 3.2), i.e. declaring an empty cell true. When that happens, the search procedure finishes in the false cell, and it is natural to try to keep the probability of such an event low enough. On the other hand, dwelling in a true cell may also end up with non-zero probability by the wrong decision: missing the signal and transition to the next (empty) cell, which had been already examined earlier. This makes the search procedure cyclic: if it is not finished after the first scanning of the uncertainty region, a second one is performed and so on, each of the successive restarts initiating a new search cycle. Below we accept that the sought signal is present at the receiver input permanently so that the number of possible cycles has no upper limit. It is seen from Figure 8.3 that if the search system comes safely to a true cell there are two possible routes from it: correct decision (and finishing search) with detection probability pd or missing signal with probability 1 pd . The latter event entails only continuing the search by the next cycle of testing and has no negative consequences except for the extra time spent before the acquisition. Dwelling in an empty cell also has two possible outcomes: correctly declaring it false, accompanied by transferring to the next one with probability 1 pf , or recognizing it true with false alarm probability pf . In comparison to signal missing, this second error is more catastrophic, since the wrong code phase delivered by the search means that all the operations performed by the receiver afterwards are useless. To secure low risk of this event every decision that the code phase is found is typically rechecked at the cost of additional dwelling (see the next section) in the suspicious cell, but nevertheless some non-zero probability remains of terminating the search in the wrong cell.
Let us call a search step every dwelling in some cell ending with the decision to either prolong or stop the search. It is seen directly from Figure 8.3 that when the search starts at cell number one (most remote from the true one) it may stop at the tth false cell (t ¼ 1, 2, . . . , M 1) after mM þ t steps, and in the true cell after mM þ M ¼ (m þ 1)M steps, where m ¼ 0, 1, . . . is the number of complete ‘idle’ search cycles, i.e. passages across the uncertainty region preceding the final (m þ 1th) cycle, at which the search stops in either a false or true cell. Then reading Figure 8.3 as a flow chart produces the following equation for probability p(s) of finishing the search after s steps:
p s |
8 f ð f |
Þ ð d Þð f Þ |
i |
|
m |
¼ |
þ ¼ |
. . . |
8:1 |
|||
|
|
|
|
h |
|
m; s mM t; t 1; 2; |
|
|
||||
ð Þ ¼ |
|
p 1 p t 1 1 p 1 p M 1 |
|
; M 1 |
ð Þ |
|||||||
> pd 1 pf |
|
M 1 |
1 pd 1 pf M 1 |
|
|
; s mM M |
|
|||||
|
< |
|
|
|
hð Þð Þ |
|
i |
|
|
|
|
|
|
> |
ð Þ |
|
|
|
¼ |
þ |
|
|
|||
|
: |
|
|
|
|
|
|
|
|
|
|
|

256 |
Spread Spectrum and CDMA |
|
|
where m ¼ 0, 1, . . . . The events (and only those ones) whose probabilities are expressed by the second row of (8.1) all imply finishing the search with a correct estimation of code phase. Therefore, the overall probability Pc1 (the index ‘1’ indicates that the search starts from the first cell) of correct search outcome (correct acquisition) is just the sum of all these probabilities over the whole range of m, i.e. the sum of the geometric progression with the ratio (1 pd )(1 pf )M 1:
P |
|
p |
|
1 |
|
p |
|
M 1 |
1 |
|
m |
pd ð1 pf ÞM 1 |
|
¼ |
d ð |
|
f Þ |
m¼0 h |
i |
¼ |
|||||||
c1 |
|
|
|
|
1 ð1 pd Þð1 pf ÞM 1 |
||||||||
|
|
|
|
|
|
|
|
|
X |
|
|
|
Another important parameter is the average number of steps s1 of the search:
1
X
s1 ¼ spðsÞ ¼ mM þ t
s¼1
ð8:2Þ
ð8:3Þ
where again index ‘1’ points at the starting cell number one. In equation (8.3) m stands for the average number of idle search cycles running before the final one, while t denotes the average number of steps within the last cycle finishing in either a false or true cell. The probability of an individual cycle being idle is a product of the probabilities of nonstopping in all M 1 empty cells and a unique true cell, i.e. (1 pd )(1 pf )M 1. Consequently, the probability p(m) of exactly m idle cycles elapsing before the search stops is:
h ih im
pðmÞ ¼ 1 ð1 pd Þð1 pf ÞM 1 ð1 pd Þð1 pf ÞM 1 ; m ¼ 0; 1; . . . ð8:4Þ
As is seen, probability distribution p(m) obeys the geometric law, whose expectation is well known, yet bearing in mind further needs we show how it is found through the generating function [14,66]:
1
X
gmðzÞ ¼ zm ¼ zmpðmÞ
m¼0
The derivatives of the generating function at the point z ¼ 1 allow calculating moments of an associated random variable. In particular:
dgmðzÞ dz z¼1
For a generic geometric distribution p(l ) ¼ al(1 a), l ¼ 0, 1, . . . ; 0 < a < 1, the generating function is obtained by summation of a geometric progression:
g |
z |
|
|
1 zlal |
|
1 |
|
a |
Þ ¼ |
1 a |
|
|
|||||||||
|
lð |
Þ ¼ l 0 |
|
ð |
|
|
|
1 za |
|
|
|||||||||||
|
|
|
|
¼ |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
X |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
so that after differentiation: |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
a |
1 aÞ |
|
|
|
|
|
|
|
a |
|
|
|
|
||||
|
|
l |
|
|
|
|
|
|
|
|
|
8:5 |
|
||||||||
|
|
¼ |
1ð |
|
|
|
¼ 1 |
|
|
|
|
Þ |
|||||||||
|
|
|
|
za |
|
2 |
|
|
|
a |
ð |
||||||||||
|
|
|
|
ð |
|
Þ |
|
|
z |
1 |
|
|
|
|
|
|
|||||
|
|
|
|
|
|
|
|
¼ |
|
|
|
|
|
|
|
|
|
|
|||
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|

Signal acquisition and tracking |
257 |
|
|
Comparing a generic geometric law with distribution (8.4) shows readily that substitution a ¼ (1 pd )(1 pf )M 1 in (8.5) produces the desired expectation m:
|
¼ |
|
ð1 pd Þð1 pf ÞM 1 |
8:6 |
Þ |
|
m |
|
|||||
1 ð1 pd Þð1 pf ÞM 1 |
||||||
|
ð |
To find the second term t in (8.3) note that the probability of terminating a final cycle in an empty cell number t regardless of how many idle cycles preceded may be found by summation in m of all probabilities of the first row in (8.1) (see also Figure 8.3), while the probability of safely reaching the unique (Mth) true cell and stopping in it (again, regardless of the number of preceding idle cycles) is just (8.2). Thus, the probability distribution p(t) of the number of steps t within the final cycle is:
|
8 pf ð1 pf Þt 1 m10 |
ð1 pd |
Þð1 pf ÞM 1 |
¼ |
1 |
|
1pf ð pd 1f Þ |
|
pf |
M 1 ; |
||||||||||||
|
|
|
|
|
¼ h |
|
|
|
|
|
i |
m |
|
ð |
1 |
p |
|
t 1 |
Þ |
|
||
|
|
|
|
|
|
|
|
|
|
|
|
|
Þð |
|
|
|
||||||
p t |
> |
|
|
|
X |
|
|
|
|
|
|
|
|
|
t 1; 2; . . . ; M 1 |
|||||||
> |
|
|
|
|
|
|
|
|
|
|
|
|
|
|||||||||
|
> |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
ð Þ ¼ |
> |
|
|
|
|
|
M 1 |
|
|
|
|
|
|
|
¼ |
|
|
|
|
|
|
|
> |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
||
|
> |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
< P |
c1 |
¼ 1 |
pd 1 pf Þ |
|
M 1 |
; t |
¼ |
M |
|
|
|
|
|
|
|
|
|
|
|||
|
> |
1 |
ð pd 1 pf |
|
|
|
|
|
|
|
|
|
|
|
|
|
||||||
|
> |
|
ð |
|
|
Þð |
Þ |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
> |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|||||
|
> |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
> |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
>
:
The generating function of this probability distribution is:
|
M |
|
|
|
|
|
|
|
|
|
|
pf |
|
|
|
|
|
|
M 1 |
|
|
|
|||
|
X |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
X |
|
|
|
||||
ztpðtÞ ¼ 1 |
ð |
1 |
|
pd |
Þð |
1 |
|
pf |
Þ |
M 1 |
|
|
|
||||||||||||
gtðzÞ ¼ |
|
|
|
|
|
|
|
|
|
|
ztð1 pf Þt 1 þ zM Pc1 |
||||||||||||||
|
t¼1 |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
t¼1 |
|
|
|
|
|
|
|
|
|
pf |
|
|
|
|
|
|
|
|
|
|
z zM ð1 pf ÞM 1 |
þ |
zMP |
|
||||||
¼ 1 |
|
1 |
pd |
1 |
|
pf |
Þ |
M 1 |
|
c1 |
|||||||||||||||
|
|
|
1 zð1 pf Þ |
|
|||||||||||||||||||||
|
|
ð |
|
Þð |
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
|
Differentiating gt(z) at the point z ¼ 1 gives, after some elementary algebra:
t ¼ 1 ð1 pf ÞM Mpf ð1 pd Þð1 pf ÞM 1 pf ½1 ð1 pd Þð1 pf ÞM 1&
Then using (8.6) and (8.7) in (8.3) ends in the average number of steps:
1 ð1 pf ÞM
s1 ¼ pf ½1 ð1 pd Þð1 pf ÞM 1&
ð8:7Þ
ð8:8Þ
Let us now abandon our initial assumption about a starting cell and consider how beginning the search in a cell number r affects the results above. In this case the partial cycle (attribute it as number zero) arises spanning M r empty cells plus one true cell. The following events are possible within this cycle: finishing the search at a false tth cell with probability p0(tjr) ¼ pf (1 pf )t r, t ¼ r, r þ 1, . . . , M 1, finishing it in the true cell with probability p0(t ¼ Mjr) ¼ pd (1 pf )M r, and, lastly, missing the signal and