
- •Contents
- •Preface
- •1 Spread spectrum signals and systems
- •1.1 Basic definition
- •1.2 Historical sketch
- •2 Classical reception problems and signal design
- •2.1 Gaussian channel, general reception problem and optimal decision rules
- •2.2 Binary data transmission (deterministic signals)
- •2.3 M-ary data transmission: deterministic signals
- •2.4 Complex envelope of a bandpass signal
- •2.5 M-ary data transmission: noncoherent signals
- •2.6 Trade-off between orthogonal-coding gain and bandwidth
- •2.7 Examples of orthogonal signal sets
- •2.7.1 Time-shift coding
- •2.7.2 Frequency-shift coding
- •2.7.3 Spread spectrum orthogonal coding
- •2.8 Signal parameter estimation
- •2.8.1 Problem statement and estimation rule
- •2.8.2 Estimation accuracy
- •2.9 Amplitude estimation
- •2.10 Phase estimation
- •2.11 Autocorrelation function and matched filter response
- •2.12 Estimation of the bandpass signal time delay
- •2.12.1 Estimation algorithm
- •2.12.2 Estimation accuracy
- •2.13 Estimation of carrier frequency
- •2.14 Simultaneous estimation of time delay and frequency
- •2.15 Signal resolution
- •2.16 Summary
- •Problems
- •Matlab-based problems
- •3 Merits of spread spectrum
- •3.1 Jamming immunity
- •3.1.1 Narrowband jammer
- •3.1.2 Barrage jammer
- •3.2 Low probability of detection
- •3.3 Signal structure secrecy
- •3.4 Electromagnetic compatibility
- •3.5 Propagation effects in wireless systems
- •3.5.1 Free-space propagation
- •3.5.2 Shadowing
- •3.5.3 Multipath fading
- •3.5.4 Performance analysis
- •3.6 Diversity
- •3.6.1 Combining modes
- •3.6.2 Arranging diversity branches
- •3.7 Multipath diversity and RAKE receiver
- •Problems
- •Matlab-based problems
- •4 Multiuser environment: code division multiple access
- •4.1 Multiuser systems and the multiple access problem
- •4.2 Frequency division multiple access
- •4.3 Time division multiple access
- •4.4 Synchronous code division multiple access
- •4.5 Asynchronous CDMA
- •4.6 Asynchronous CDMA in the cellular networks
- •4.6.1 The resource reuse problem and cellular systems
- •4.6.2 Number of users per cell in asynchronous CDMA
- •Problems
- •Matlab-based problems
- •5 Discrete spread spectrum signals
- •5.1 Spread spectrum modulation
- •5.2 General model and categorization of discrete signals
- •5.3 Correlation functions of APSK signals
- •5.4 Calculating correlation functions of code sequences
- •5.5 Correlation functions of FSK signals
- •5.6 Processing gain of discrete signals
- •Problems
- •Matlab-based problems
- •6 Spread spectrum signals for time measurement, synchronization and time-resolution
- •6.1 Demands on ACF: revisited
- •6.2 Signals with continuous frequency modulation
- •6.3 Criterion of good aperiodic ACF of APSK signals
- •6.4 Optimization of aperiodic PSK signals
- •6.5 Perfect periodic ACF: minimax binary sequences
- •6.6 Initial knowledge on finite fields and linear sequences
- •6.6.1 Definition of a finite field
- •6.6.2 Linear sequences over finite fields
- •6.6.3 m-sequences
- •6.7 Periodic ACF of m-sequences
- •6.8 More about finite fields
- •6.9 Legendre sequences
- •6.10 Binary codes with good aperiodic ACF: revisited
- •6.11 Sequences with perfect periodic ACF
- •6.11.1 Binary non-antipodal sequences
- •6.11.2 Polyphase codes
- •6.11.3 Ternary sequences
- •6.12 Suppression of sidelobes along the delay axis
- •6.12.1 Sidelobe suppression filter
- •6.12.2 SNR loss calculation
- •6.13 FSK signals with optimal aperiodic ACF
- •Problems
- •Matlab-based problems
- •7 Spread spectrum signature ensembles for CDMA applications
- •7.1 Data transmission via spread spectrum
- •7.1.1 Direct sequence spreading: BPSK data modulation and binary signatures
- •7.1.2 DS spreading: general case
- •7.1.3 Frequency hopping spreading
- •7.2 Designing signature ensembles for synchronous DS CDMA
- •7.2.1 Problem formulation
- •7.2.2 Optimizing signature sets in minimum distance
- •7.2.3 Welch-bound sequences
- •7.3 Approaches to designing signature ensembles for asynchronous DS CDMA
- •7.4 Time-offset signatures for asynchronous CDMA
- •7.5 Examples of minimax signature ensembles
- •7.5.1 Frequency-offset binary m-sequences
- •7.5.2 Gold sets
- •7.5.3 Kasami sets and their extensions
- •7.5.4 Kamaletdinov ensembles
- •Problems
- •Matlab-based problems
- •8 DS spread spectrum signal acquisition and tracking
- •8.1 Acquisition and tracking procedures
- •8.2 Serial search
- •8.2.1 Algorithm model
- •8.2.2 Probability of correct acquisition and average number of steps
- •8.2.3 Minimizing average acquisition time
- •8.3 Acquisition acceleration techniques
- •8.3.1 Problem statement
- •8.3.2 Sequential cell examining
- •8.3.3 Serial-parallel search
- •8.3.4 Rapid acquisition sequences
- •8.4 Code tracking
- •8.4.1 Delay estimation by tracking
- •8.4.2 Early–late DLL discriminators
- •8.4.3 DLL noise performance
- •Problems
- •Matlab-based problems
- •9 Channel coding in spread spectrum systems
- •9.1 Preliminary notes and terminology
- •9.2 Error-detecting block codes
- •9.2.1 Binary block codes and detection capability
- •9.2.2 Linear codes and their polynomial representation
- •9.2.3 Syndrome calculation and error detection
- •9.2.4 Choice of generator polynomials for CRC
- •9.3 Convolutional codes
- •9.3.1 Convolutional encoder
- •9.3.2 Trellis diagram, free distance and asymptotic coding gain
- •9.3.3 The Viterbi decoding algorithm
- •9.3.4 Applications
- •9.4 Turbo codes
- •9.4.1 Turbo encoders
- •9.4.2 Iterative decoding
- •9.4.3 Performance
- •9.4.4 Applications
- •9.5 Channel interleaving
- •Problems
- •Matlab-based problems
- •10 Some advancements in spread spectrum systems development
- •10.1 Multiuser reception and suppressing MAI
- •10.1.1 Optimal (ML) multiuser rule for synchronous CDMA
- •10.1.2 Decorrelating algorithm
- •10.1.3 Minimum mean-square error detection
- •10.1.4 Blind MMSE detector
- •10.1.5 Interference cancellation
- •10.1.6 Asynchronous multiuser detectors
- •10.2 Multicarrier modulation and OFDM
- •10.2.1 Multicarrier DS CDMA
- •10.2.2 Conventional MC transmission and OFDM
- •10.2.3 Multicarrier CDMA
- •10.2.4 Applications
- •10.3 Transmit diversity and space–time coding in CDMA systems
- •10.3.1 Transmit diversity and the space–time coding problem
- •10.3.2 Efficiency of transmit diversity
- •10.3.3 Time-switched space–time code
- •10.3.4 Alamouti space–time code
- •10.3.5 Transmit diversity in spread spectrum applications
- •Problems
- •Matlab-based problems
- •11 Examples of operational wireless spread spectrum systems
- •11.1 Preliminary remarks
- •11.2 Global positioning system
- •11.2.1 General system principles and architecture
- •11.2.2 GPS ranging signals
- •11.2.3 Signal processing
- •11.2.4 Accuracy
- •11.2.5 GLONASS and GNSS
- •11.2.6 Applications
- •11.3 Air interfaces cdmaOne (IS-95) and cdma2000
- •11.3.1 Introductory remarks
- •11.3.2 Spreading codes of IS-95
- •11.3.3 Forward link channels of IS-95
- •11.3.3.1 Pilot channel
- •11.3.3.2 Synchronization channel
- •11.3.3.3 Paging channels
- •11.3.3.4 Traffic channels
- •11.3.3.5 Forward link modulation
- •11.3.3.6 MS processing of forward link signal
- •11.3.4 Reverse link of IS-95
- •11.3.4.1 Reverse link traffic channel
- •11.3.4.2 Access channel
- •11.3.4.3 Reverse link modulation
- •11.3.5 Evolution of air interface cdmaOne to cdma2000
- •11.4 Air interface UMTS
- •11.4.1 Preliminaries
- •11.4.2 Types of UMTS channels
- •11.4.3 Dedicated physical uplink channels
- •11.4.4 Common physical uplink channels
- •11.4.5 Uplink channelization codes
- •11.4.6 Uplink scrambling
- •11.4.7 Mapping downlink transport channels to physical channels
- •11.4.8 Downlink physical channels format
- •11.4.9 Downlink channelization codes
- •11.4.10 Downlink scrambling codes
- •11.4.11 Synchronization channel
- •11.4.11.1 General structure
- •11.4.11.2 Primary synchronization code
- •11.4.11.3 Secondary synchronization code
- •References
- •Index
Time measurement, synchronization and time-resolution |
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same role among all polynomials as prime numbers among integers. Not all arbitrary irreducible polynomials need to be primitive, although in a special case p ¼ 2 and prime 2n 1 all irreducible polynomials are primitive. Proving the necessity and sufficiency of choosing feedback as indicated above would require some more algebra, which could take us far away from our main purpose. An interested reader may find the details in numerous sources (e.g. [31,32]).
Primitive polynomials are extensively tabulated in books on modern algebra and coding theory or (mostly for p ¼ 2) spread spectrum telecommunication [5,6,18,32]. Another option is a computer search, which is not at all a difficult task (e.g. Problem 6.47). In particular, ready-made functions for finding primitive polynomials are present in the Matlab Communications Toolbox.
As a whole, designing an m-sequence generator is pretty straightforward. When p is selected, a necessary length L determines the memory n, and finding an appropriate primitive polynomial exhausts the issue.
Commenting again on Examples 6.6.1 and 6.6.2, note that the binary m-sequence of length 7 is built based on the primitive polynomial f (x) ¼ x3 þ x þ 1 over GF(2), while the primitive polynomial over GF(3) used to generate the ternary sequence of length 26 is f (x) ¼ x3 þ 2x þ 1.
6.7 Periodic ACF of m-sequences
The results of the previous section lead quickly to the minimax binary sequences with ACF meeting (6.12). Consider a binary m-sequence fdig of memory n, i.e. length L ¼ 2n 1. Let us map its symbols 0, 1 onto a binary alphabet 1 according to the rule:
ai ¼ ð 1Þdi ¼ |
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ð6:15Þ |
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where in raising ( 1) to the degree di the latter is treated as though it is a real number 0 or 1. The sequence faig of real binary symbols 1 thus obtained has period N ¼ L ¼ 2n 1 and is a one-to-one image of the original binary m-sequence fdig. It is natural to keep for it the same name binary m-sequence as well. When the confusion is risky, a supplementary label like binary f 1g sequence versus binary f0, 1g sequence may be used. Let us find the non-normalized periodic ACF (6.7) of faig:
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Now the shift-and-add property of binary f0, 1g m-sequences may be brought in. Addition in the exponent here may be treated as modulo 2, since it will produce the same result of exponentiation as an ordinary arithmetic summation. But then fd 0ig ¼ fdi þ di mg is a binary f0, 1g m-sequence of period L whenever m 6¼0modL,

168 |
Spread Spectrum and CDMA |
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or an all-zero sequence otherwise. Due |
to the balance property, one period of |
fd i0g ¼ fdi þ di mg contains L0 ¼ 2n 1 1 |
zeros and L1 ¼ 2n 1 ones, therefore the |
sum in (6.16) contains L0 plus ones and L1 minus ones if m 6¼0modN, so that:
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As is seen this coincides exactly with (6.12), confirming that binary m-sequences are minimax ones.3
Example 6.7.1. Consider again the sequence of Example 6.6.1. Its mapping onto the alphabet f1g in accordance with (6.15) produces the f1g m-sequence 1, þ 1, þ 1, 1, þ1, 1, 1, . . . . Table 6.3, which contains only the minimum necessary number of entries, illustrates calculating the periodic ACF of the sequence. It is interesting also to study the matched filter processing of a discrete signal modulated by this binary sequence. Figure 6.14 presents such a filter matched with one period of a baseband rectangular-chip periodic signal. All units in this structure are absolutely similar to those of Figure 6.7. Waveforms at characteristic points of the filter are shown in Figure 6.15. As is seen, the output waveform has mainlobes repeating with period ND and a uniform sidelobe background of negative polarity seven times smaller than the mainlobe level.
Table 6.3 Calculating periodic ACF of the binary m-sequence ( þ þ þ )
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Figure 6.14 Matched filter for the binary m-sequence of length N ¼ 7
3 Generalization of mapping (6.15) onto sequences over GF(p), p 2 is ai ¼ exp (j2 di/p), resulting in polyphase (p-phase) code, whose periodic ACF again satisfies (6.12). However, polyphase codes of this sort with p > 2 are of less practical interest than minimax binary sequences.

Time measurement, synchronization and time-resolution |
169 |
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Figure 6.15 Matched filtering of periodic binary m-sequence of length N ¼ 7
Binary m-sequences are among the most popular discrete signals in modern information technology due to their optimal periodic correlation properties and very simple generating and processing circuitry. Probably one of the most demonstrative examples of their practical involvement is 2G cdmaOne (IS-95) mobile phone, where m-sequences of various lengths are used as pilot signals for initial synchronization, base station signal multiplexing and data scrambling.
In addition, m-sequences represent the basis for deriving other important signal families (Kasami, Gold and others; see Chapter 7).
At the same time, the set of lengths N ¼ 2n 1 ¼ 3, 7, 15, 31, 63, 127, 255, 511, 1023, . . .
where these sequences exist, is rather sparse, which sometimes may appear technologically obstructive. This is a reason for studying one more interesting class of binary minimax sequences, but before attending to that some additional insight into finite fields is required.

170 |
Spread Spectrum and CDMA |
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6.8 More about finite fields
Let us take some element x of a finite field GF(p) and multiply it with itself m times, designating the result as the mth power of x:
x x . . . x ¼ xm
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m times
The ordinary rules of handling powers in conventional algebra remain valid in any field, including finite ones. In particular:
xmxn ¼ x x . . . x x x . . . x ¼ x x . . . x ¼ xmþn; ðxmÞn¼ xm xm . . . xm ¼ xmn
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the inverse of any non-zero element give: x0 ¼ 1 and ðxmÞ 1¼ x m
Example 6.8.1. In the field GF(5) (see tables of Figure 6.11):
20 ¼ 1; 21 ¼ 2; 22 ¼ 2 2 ¼ 4; 23 ¼ 22 2 ¼ 4 2 ¼ 3; 24 ¼ 23 3 ¼ 3 2 ¼ 1 2 1 ¼ 3; 2 2 ¼ 2 1 2¼ 32 ¼ 4; 2 3 ¼ 2 1 3¼ 33 ¼ 4 3 ¼ 2; 2 4 ¼ 2 1 4¼ 34 ¼ 2 3 ¼ 1
Consider now successive degrees of the element x 6¼0 of GF(p): x0 ¼ 1, x1, x2, . . .. Since all terms of this series belong to GF(p), i.e. finite field, they cannot all be different, and therefore equality holds xi ¼ xk ) xi k ¼ 1 for some i > k. Suppose that the elementexists whose first p 1 powers 0 ¼ 1, 1, 2, . . . , p 2 are all different. Since p 1 is just the number of non-zero elements of GF(p), the powers above are exactly all non-zero elements of GF(p). Therefore, the element , if it really exists, allows constructing the whole field GF(p) but the zero element by just raising to powers 0, 1, . . . , p 2. Such an element is called a primitive one.
One of the most important facts about finite fields is that they all contain a primitive element. Proof of this result may be found in many algebraic or coding theory textbooks
Time measurement, synchronization and time-resolution |
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(e.g. [30,32,33]). A primitive element is not unique: in any finite field whose order exceeds 3, more than one primitive element is present. For instance, as is seen from Example 6.8.1, both 2 and 3 are primitive elements in GF(5).
Since for a primitive element powers 0 ¼ 1, 1, 2, . . . , p 2 exhaust all non-zero elements of GF(p), p 1 should be equal to one of them. Actually it cannot be equal to anything but 1, because p 1 ¼ l with 0 < l p 2 means that p 1 l ¼ 1. This is not possible, since 1 < p 1 l < p 1 and among elements 1, 2, . . . , p 2 none may be equal to 1. Hence, p 1 ¼ 1. Now it is easy to see that the same is true for any non-zero element of a finite field, not only for a primitive one. Indeed, every non-zero element x of GF(p) is the lth power of a primitive element for a proper integer l: x ¼ l, so that (small Fermat theorem):
xp 1 ¼ l p 1¼ lðp 1Þ ¼ p 1 l¼ 1 |
ð6:17Þ |
The next entity bears quite a natural name, fully consistent with the categories of ordinary algebra. The integer exponent l, which after raising to it produces x ¼ l, is the logarithm of x to the base with a conventional designation log x. Therefore,
log x ¼ x.
Now consider only the prime fields of an odd order (p > |
2) and introduce a new |
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notion of the binary character (x) of a non-zero element x defined as follows: |
ð |
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Þ |
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ð |
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Þ ¼ 1; |
log x 6¼0 mod2 |
¼ ð |
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Þ |
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x |
1; |
log x ¼ 0 mod2 |
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1 |
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log x |
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6:18 |
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Clearly, the binary character is simply a mapping of the finite field GF(p) onto a pair of real numbers fþ1, 1g, transforming non-zero element x into þ1 if its logarithm is even and into 1 otherwise. Note that this mapping does not depend on a specific choice of a primitive element (Problem 6.24). The following properties of a binary character will be used further:
1. The character of the unit element of GF(p) is always one:
ð1Þ ¼ 1: |
ð6:19Þ |
This is true because 0 ¼ 1 ) log 1 ¼ 0.
2.The character is a multiplicative function, i.e. the character of a product of two nonzero elements is a product of their characters. Indeed, from (6.17) and (6.18):
ðxyÞ ¼ ð 1Þlog ðxyÞ ¼ ð 1Þlog xþlog y ¼ ð 1Þlog x ð 1Þlog y ¼ ðxÞ ðyÞ ð6:20Þ
3. Balance property: the sum of characters of all non-zero elements of GF(p) is zero:
p 1 |
p 1 |
|
X |
X |
ð6:21Þ |
ðxÞ ¼ |
ð 1Þlog x ¼ 0: |
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x¼1 |
x¼1 |
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To prove this equality note that when x assumes all p 1 non-zero values, log x runs in some order over the range of p 1 integers 0, 1, . . . , p 2. Due to the oddness